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12-output clock generator with integrated 2.5 ghz vco ad9517-1 rev. a information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. specifications subject to change without notice. no license is granted by implication or otherwise under any patent or patent rights of analog devices. trademarks and registered trademarks are the property of their respective owners. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781.329.4700 www.analog.com fax: 781.461.3113 ?2007C2010 analog devices, inc. all rights reserved. features low phase noise, phase-locked loop (pll) on-chip vco tunes from 2.30 ghz to 2.65 ghz external vco/vcxo to 2.4 ghz optional 1 differential or 2 single-ended reference inputs reference monitoring capability auto and manual reference switchover/holdover modes autorecover from holdover accepts lvpecl, lvds, or cmos references to 250 mhz programmable delays in path to pfd digital or analog lock detect, selectable 2 pairs of 1.6 ghz lvpecl outputs each output pair shares a 1-to-32 divider with coarse phase delay additive output jitter 225 fs rms channel-to-channel skew paired outputs of <10 ps 2 pairs of 800 mhz lvds clock outputs each output pair shares two cascaded 1-to-32 dividers with coarse phase delay additive output jitter 275 fs rms fine delay adjust (t) on each lvds output eight 250 mhz cmos outputs (two per lvds output) automatic synchronization of all outputs on power-up manual synchronization of outputs, as needed serial control port available in a 48-lead lfcsp applications low jitter, low phase noise clock distribution clocking high speed adcs, dacs, ddss, ddcs, ducs, mxfes high performance wireless transceivers 10/40/100 gb/sec networking line cards, including sonet, synchronous ethernet, otu2/3/4 high performance instrumentation broadband infrastructure ate general description the ad9517-1 1 provides a multi-output clock distribution function with subpicosecond jitter performance, along with an on-chip pll and vco. the on-chip vco tunes from 2.30 ghz to 2.65 ghz. optionally, an external vco/vcxo of up to 2.4 ghz can be used. the ad9517-1 emphasizes low jitter and phase noise to maximize data converter performance, and it can benefit other applications with demanding phase noise and jitter requirements. functional block diagram refin ref1 ref2 clk lf switchover and monitor pll divider and muxs cp vco status monitor lvpecl lvpecl lvds/cmos lvds/cmos serial control port and digital logic ad9517-1 out0 out1 out2 out3 out4 out5 out6 out7 div/ div/ div/ div/ div/ div/ 06425-001 t t t t figure 1. the ad9517-1 features four lvpecl outputs (in two pairs) and four lvds outputs (in two pairs). each lvds output can be reconfigured as two cmos outputs. the lvpecl outputs operate to 1.6 ghz, the lvds outputs operate to 800 mhz, and the cmos outputs operate to 250 mhz. each pair of outputs has dividers that allow both the divide ratio and coarse delay (or phase) to be set. the range of division for the lvpecl outputs is 1 to 32. the lvds/cmos outputs allow a range of divisions up to a maximum of 1024. the ad9517-1 is available in a 48-lead lfcsp and can be operated from a single 3.3 v supply. an external vco, which requires an extended voltage range, can be accommodated by connecting the charge pump supply (vcp) to 5 v. a separate lvpecl power supply can be from 2.5 v to 3.3 v (nominal). the ad9517-1 is specified for operation over the industrial range of ?40c to +85c. 1 ad9517 is used throughout the data sh eet to refer to all the members of the ad9517 family. however, when ad9517-1 is used, it is referring to that specific member of the ad9517 family.
ad9517-1 rev. a | page 2 of 80 table of contents features .............................................................................................. 1 ? applications ....................................................................................... 1 ? general description ......................................................................... 1 ? functional block diagram .............................................................. 1 ? revision history ............................................................................... 3 ? specifications ..................................................................................... 4 ? power supply requirements ....................................................... 4 ? pll characteristics ...................................................................... 4 ? clock inputs .................................................................................. 6 ? clock outputs ............................................................................... 6 ? timing characteristics ................................................................ 7 ? clock output additive phase noise (distribution only; vco divider not used) .............................................................. 8 ? clock output absolute phase noise (internal vco used) .... 9 ? clock output absolute time jitter (clock generation using internal vco) .................................................................. 10 ? clock output absolute time jitter (clock cleanup using internal vco) ............................................................................. 10 ? clock output absolute time jitter (clock generation using external vcxo) .............................................................. 10 ? clock output additive time jitter (vco divider not used) ..................................................................................... 11 ? clock output additive time jitter (vco divider used) ..... 11 ? delay block additive time jitter .............................................. 12 ? serial control port ..................................................................... 12 ? pd , sync , and reset pins ..................................................... 13 ? ld, status, and refmon pins ............................................ 13 ? power dissipation ....................................................................... 14 ? timing diagrams ............................................................................ 15 ? absolute maximum ratings .......................................................... 16 ? thermal resistance .................................................................... 16 ? esd caution................................................................................ 16 ? pin configuration and function descriptions ........................... 17 ? typical performance characteristics ........................................... 19 ? terminology .................................................................................... 25 ? detailed block diagram ................................................................ 26 ? theory of operation ...................................................................... 27 ? operational configurations ...................................................... 27 ? digital lock detect (dld) ....................................................... 36 ? clock distribution ..................................................................... 40 ? reset modes ................................................................................ 48 ? power-down modes .................................................................. 49 ? serial control port ......................................................................... 50 ? serial control port pin descriptions ....................................... 50 ? general operation of serial control port ............................... 50 ? the instruction word (16 bits) ................................................ 51 ? msb/lsb first transfers ........................................................... 51 ? thermal performance .................................................................... 54 ? control registers ............................................................................ 55 ? control register map overview .............................................. 55 ? control register map descriptions ......................................... 58 ? applications information .............................................................. 75 ? frequency planning using the ad9517 .................................. 75 ? using the ad9517 outputs for adc clock applications .... 75 ? lvpecl clock distribution ..................................................... 76 ? lvds clock distribution .......................................................... 76 ? cmos clock distribution ........................................................ 77 ? outline dimensions ....................................................................... 78 ? ordering guide .......................................................................... 78 ?
ad9517-1 rev. a | page 3 of 80 revision history 1/10rev. 0 to rev. a added 48-lead lfcsp package (cp-48-8) .................... universal changes to features, applications, and general description ..... 1 change to cprset pin resistor parameter .................................. 4 changes to table 4 ............................................................................ 6 changes to v cp supply parameter ................................................. 14 changes to table 19 ........................................................................ 16 added exposed paddle notation to figure 6; changes to table 20 ............................................................................................. 17 change to high frequency clock distributionclk or external vco > 1600 mhz section; change to table 22 .......... 27 changes to table 24 ........................................................................ 29 change to configuration and register settings section ............ 31 change to phase frequency detector (pfd) section ................ 32 changes to charge pump (cp), on-chip vco, pll external loop filter, and pll reference inputs sections ......... 33 change to figure 46; added figure 47 ......................................... 33 changes to reference switchover and vcxo/vco feedback divider np, a, b, r sections .................................... 34 changes to table 28 ........................................................................ 35 change to holdover section .......................................................... 37 changes to vco calibration section ........................................... 39 changes to clock distribution section ........................................ 40 change to clock frequency division section; change to table 34 .......................................................................... 41 changes to channel dividerslvds/cmos outputs section; change to table 39 ........................................................... 43 change to write section ................................................................ 50 change to msb/lsb first transfers ............................................. 51 change to figure 64 ........................................................................ 52 added thermal performance section .......................................... 54 changes to 0x003 register address .............................................. 55 changes to table 52 ........................................................................ 58 changes to table 54 ........................................................................ 59 changes to table 55 ........................................................................ 65 changes to table 56 ........................................................................ 67 changes to table 57 ........................................................................ 69 changes to table 58 ........................................................................ 71 changes to table 59 ........................................................................ 72 changes to table 60 and table 61 ................................................. 74 added frequency planning using the ad9517 section ............ 75 changes to figure 70 and figure 72; added figure 71 .............. 76 changes to lvds clock distribution section ............................ 76 added exposed paddle notation to outline dimensions ......... 78 changes to ordering guide ........................................................... 78 7/07revision 0: initial version
ad9517-1 rev. a | page 4 of 80 specifications typical (typ) is given for v s = v s_lvpecl = 3.3 v 5%; v s v cp 5.25 v; t a = 25c; r set = 4.12 k; cp rset = 5.1 k, unless otherwise noted. minimum (min) and maximum (max) values are given over full v s and t a (?40c to +85c) variation. power supply requirements table 1. parameter min typ max unit test conditions/comments v s 3.135 3.3 3.465 v 3.3 v 5% v s_lvpecl 2.375 v s v nominally 2.5 v to 3.3 v 5% v cp v s 5.25 v nominally 3.3 v to 5.0 v 5% rset pin resistor 4.12 k sets intern al biasing currents; connect to ground cprset pin resistor 2.7 5.1 k sets internal cp current range, nominally 4.8 ma (cp_lsb = 600 a); actual current can be calculated by cp_lsb = 3.06/cprset; connect to ground bypass pin capacitor 220 nf bypass for internal ldo regulator; necessary for ldo stability; connect to ground pll characteristics table 2. parameter min typ max unit test conditions/comments vco (on-chip) frequency range 2300 2650 mhz see figure 15 vco gain (k vco ) 50 mhz/v see figure 10 tuning voltage (v t ) 0.5 v cp ? 0.5 v v cp v s when using internal vco; outside of this range, the cp spurs may increase due to cp up/down mismatch frequency pushing (open loop) 1 mhz/v phase noise @ 100 khz offset ?105 dbc/hz f = 2475 mhz phase noise @ 1 mhz offset ?124 dbc/hz f = 2475 mhz reference inputs differential mode (refin, refin ) differential mode (can accommodate single-ended input by ac grounding undriven input) input frequency 0 250 mhz frequencies below about 1 mhz should be dc-coupled; be careful to match v cm (self-bias voltage) input sensitivity 250 mv p-p pll figure of merit increases with increasing slew rate; see figure 14 self-bias voltage, refin 1.35 1.60 1.75 v self-bias voltage of refin 1 self-bias voltage, refin 1.30 1.50 1.60 v self-bias voltage of refin 1 input resistance, refin 4.0 4.8 5.9 k self-biased 1 input resistance, refin 4.4 5.3 6.4 k self-biased 1 dual single-ended mode (ref1, ref2) two single-ended cmos-compatible inputs input frequency (ac-coupled) 20 250 mhz slew rate > 50 v/s input frequency (dc-coupled) 0 250 mhz slew rate > 50 v/s; cmos levels input sensitivity (ac-coupled) 0.8 v p-p should not exceed v s p-p input logic high 2.0 v input logic low 0.8 v input current ?100 +100 a input capacitance 2 pf each pin, refin/ refin (ref1/ref2) phase/frequency detector (pfd) pfd input frequency 100 mhz antiba cklash pulse width = 1.3 ns, 2.9 ns 45 mhz antibacklash pulse width = 6.0 ns antibacklash pulse width 1.3 ns register 0x017[1:0] = 01b 2.9 ns register 0x017[1:0] = 00b; register 0x17[1:0] = 11b 6.0 ns register 0x017[1:0] = 10b
ad9517-1 rev. a | page 5 of 80 parameter min typ max unit test conditions/comments charge pump (cp) i cp sink/source programmable high value 4.8 ma with cp rset = 5.1 k low value 0.60 ma absolute accuracy 2.5 % cp v = v cp /2 v cp rset range 2.7/10 k i cp high impedance mode leakage 1 na sink-and-source current matching 2 % 0.5 < cp v < v cp ? 0.5 v i cp vs. cp v 1.5 % 0.5 < cp v < v cp ? 0.5 v i cp vs. temperature 2 % cp v = v cp /2 v prescaler (part of n divider) prescaler input frequency p = 1 fd 300 mhz p = 2 fd 600 mhz p = 3 fd 900 mhz p = 2 dm (2/3) 600 mhz p = 4 dm (4/5) 1000 mhz p = 8 dm (8/9) 2400 mhz p = 16 dm (16/17) 3000 mhz p = 32 dm (32/33) 3000 mhz prescaler output frequency 300 mhz a, b coun ter input frequency (prescaler input frequency divided by p) pll divider delays register 0x 019: r, bits[5:3]; n, bits[2:0]; see table 54 000 off 001 330 ps 010 440 ps 011 550 ps 100 660 ps 101 770 ps 110 880 ps 111 990 ps noise characteristics in-band phase noise of the charge pump/phase frequency detector (in-band is within the lbw of the pll) the pll in-band phase noise floor is estimated by measuring the in-band phase noise at the output of the vco and subtracting 20 log(n) (where n is the value of the n divider) @ 500 khz pfd frequency ?165 dbc/hz @ 1 mhz pfd frequency ?162 dbc/hz @ 10 mhz pfd frequency ?151 dbc/hz @ 50 mhz pfd frequency ?143 dbc/hz pll figure of merit (fom) ?220 dbc/hz reference slew rate > 0.25 v/ns; fom +10 log(f pfd ) is an approximation of the pfd/cp in-band phase noise (in the flat region) inside the pll loop bandwidth; when running closed loop, the phase noise, as observed at the vco output, is increased by 20 log(n) pll digital lock detect window 2 signal available at ld, status, and refmon pins when selected by appropriate register settings required to lock (coincidence of edges) selected by register 0x017[1:0] and register 0x018[4] low range (abp 1.3 ns, 2.9 ns) 3.5 ns register 0x017[1:0] = 00b, 01b,11b; register 0x018[4] = 1b high range (abp 1.3 ns, 2.9 ns) 7.5 ns register 0x017[1:0] = 00b, 01b, 11b; register 0x018[4] = 0b high range (abp 6 ns) 3.5 ns register 0x017[1:0] = 10b; register 0x018[4] = 0b to unlock after lock (hysteresis) 2 low range (abp 1.3 ns, 2.9 ns) 7 ns register 0x017[1:0] = 00b, 01b, 11b; register 0x018[4] = 1b high range (abp 1.3 ns, 2.9 ns) 15 ns register 0x017[1:0] = 00b, 01b, 11b; register 0x018[4] = 0b high range (abp 6 ns) 11 ns register 0x017[1:0] = 10b; register 0x018[4] = 0b 1 refin and refin self-bias points are offset slightly to av oid chatter on an open input condition. 2 for reliable operation of the digital lock detect, the period of the pfd frequency must be greater than the unlock-after-lock time.
ad9517-1 rev. a | page 6 of 80 clock inputs table 3. parameter min typ max unit test conditions/comments clock inputs (clk, clk ) differential input input frequency 0 1 2.4 ghz high frequency distribution (vco divider) 0 1 1.6 ghz distribution only (vco divider bypassed) input sensitivity, differential 150 mv p-p measured at 2.4 ghz; jitter performance is improved with slew rates > 1 v/ns input level, differential 2 v p-p larger voltage swings may turn on the protection diodes and may degrade jitter performance input common-mode voltage, v cm 1.3 1.57 1.8 v self-biased; enables ac coupling input common-mode range, v cmr 1.3 1.8 v with 200 mv p-p signal applied; dc-coupled input sensitivity, single-ended 150 mv p-p clk ac-coupled; clk ac-bypassed to rf ground input resistance 3.9 4.7 5.7 k self-biased input capacitance 2 pf 1 below about 1 mhz, the input should be dc-coupled. care should be taken to match v cm . clock outputs table 4. parameter min typ max unit test conditions/comments lvpecl clock outputs termination = 50 to v s ? 2 v out0, out1, out2, out3 differential (out, out ) output frequency, maximum 2950 mh z using direct to output; see figure 25 output high voltage (v oh ) v s ? 1.12 v s ? 0.98 v s ? 0.84 v output low voltage (v ol ) v s ? 2.03 v s ? 1.77 v s ? 1.49 v output differential voltage (v od ) 550 790 980 mv lvds clock outputs differential termination 100 @ 3.5 ma out4, out5, out6, out7 differential (out, out ) output frequency 800 mhz the ad9517 outputs toggle at higher frequencies, but the output amplitude may not meet the v od specification differential output voltage (v od ) 247 360 454 mv v oh ? v ol measurement across a differential pair at the default amplitude setting with output driver not toggling; see figure 26 for variation over frequency delta v od 25 mv this is the absolute value of the difference between v od when the normal output is high vs. when the complementary output is high output offset voltage (v os ) 1.125 1.24 1.375 v (v oh + v ol )/2 across a differential pair delta v os 25 mv this is the absolute value of the difference between v os when the normal output is high vs. when the complementary output is high short-circuit current (i sa , i sb ) 14 24 ma output shorted to gnd cmos clock outputs out4a, out4b, out5a, out5b, out6a, out6b, out7a, out7b single-ended; termination = 10 pf output frequency 250 mhz see figure 27 output voltage high (v oh ) v s ? 0.1 v @ 1 ma load output voltage low (v ol ) 0.1 v @ 1 ma load
ad9517-1 rev. a | page 7 of 80 timing characteristics table 5. parameter min typ max unit test conditions/comments lvpecl termination = 50 to v s ? 2 v; level = 810 mv output rise time, t rp 70 180 ps 20% to 80%, measured differentially output fall time, t fp 70 180 ps 80% to 20%, measured differentially propagation delay, t pecl , clk-to-lvpecl output high frequency clock distribution configuration 835 995 1180 ps see figure 42 clock distribution configuration 773 933 1090 ps see figure 44 variation with temperature 0.8 ps/c output skew, lvpecl outputs 1 lvpecl outputs that share the same divider 5 15 ps lvpecl outputs on different dividers 13 40 ps all lvpecl outputs across mu ltiple parts 220 ps lvds termination = 100 differential; 3.5 ma output rise time, t rl 170 350 ps 20% to 80%, measured differentially 2 output fall time, t fl 160 350 ps 20% to 80%, measured differentially 2 propagation delay, t lvds , clk-to-lvds output delay off on all outputs for all divide values 1.4 1.8 2.1 ns variation with temperature 1.25 ps/c output skew, lvds outputs 1 delay off on all outputs lvds outputs that share the same divider 6 62 ps lvds outputs on different dividers 25 150 ps all lvds outputs across multiple parts 430 ps cmos termination = open output rise time, t rc 495 1000 ps 20% to 80%; c load = 10 pf output fall time, t fc 475 985 ps 80% to 20%; c load = 10 pf propagation delay, t cmos , clk-to-cmos output fine delay off for all divide values 1.6 2.1 2.6 ns variation with temperature 2.6 ps/c output skew, cmos outputs 1 fine delay off cmos outputs that share the same divider 4 66 ps all cmos outputs on different dividers 28 180 ps all cmos outputs across multiple parts 675 ps delay adjust 3 lvds and cmos shortest delay range 4 register 0x0a1 (0x0a4) (0x0a7) (0x0aa) [5:0] 101111b zero scale 50 315 680 ps register 0x0a2 (0x0a5) (0x0a8) (0x0ab) [5:0] 000000b full scale 540 880 1180 ps register 0x0a2 (0x0a5) (0x0a8) (0x0ab) [5:0] 101111b longest delay range 4 register 0x0a1 (0x0a4) (0x0a7) (0x0aa) [5:0] 000000b zero scale 200 570 950 ps register 0x0a2 (0x0a5) (0x0a8) (0x0ab) [5:0] 000000b quarter scale 1.72 2.31 2.89 ns register 0x0a2 (0x0a5) (0x0a8) (0x0ab) [5:0] 001100b full scale 5.7 8.0 10.1 ns register 0x0a2 (0x0a5) (0x0a8) (0x0ab) [5:0] 101111b delay variation with temperature short delay range 5 zero scale 0.23 ps/c full scale ?0.02 ps/c long delay range 5 zero scale 0.3 ps/c full scale 0.24 ps/c 1 this is the difference between any two similar delay pa ths while operating at the s ame voltage and temperature. 2 corresponding cmos drivers set to a for noninverting and b for inverting. 3 the maximum delay that can be used is a little less than one-half the period of the clock. a longer delay disables the output. 4 incremental delay; does not include propagation delay. 5 all delays between zero scale and full scal e can be estimated by linear interpolation.
ad9517-1 rev. a | page 8 of 80 clock output additive phase noise (distribution only; vco divider not used) table 6. parameter min typ max unit test conditions/comments clk-to-lvpecl additive phase noise distri bution section only; does not include pll and vco clk = 1 ghz, output = 1 ghz input slew rate > 1 v/ns divider = 1 @ 10 hz offset ?109 dbc/hz @ 100 hz offset ?118 dbc/hz @ 1 khz offset ?130 dbc/hz @ 10 khz offset ?139 dbc/hz @ 100 khz offset ?144 dbc/hz @ 1 mhz offset ?146 dbc/hz @ 10 mhz offset ?147 dbc/hz @ 100 mhz offset ?149 dbc/hz clk = 1 ghz, output = 200 mhz input slew rate > 1 v/ns divider = 5 @ 10 hz offset ?120 dbc/hz @ 100 hz offset ?126 dbc/hz @ 1 khz offset ?139 dbc/hz @ 10 khz offset ?150 dbc/hz @ 100 khz offset ?155 dbc/hz @ 1 mhz offset ?157 dbc/hz >10 mhz offset ?157 dbc/hz clk-to-lvds additive phase noise distrib ution section only; does not include pll and vco clk = 1.6 ghz, output = 800 mhz input slew rate > 1 v/ns divider = 2 @ 10 hz offset ?103 dbc/hz @ 100 hz offset ?110 dbc/hz @ 1 khz offset ?120 dbc/hz @ 10 khz offset ?127 dbc/hz @ 100 khz offset ?133 dbc/hz @ 1 mhz offset ?138 dbc/hz @ 10 mhz offset ?147 dbc/hz @ 100 mhz offset ?149 dbc/hz clk = 1.6 ghz, output = 400 mhz input slew rate > 1 v/ns divider = 4 @ 10 hz offset ?114 dbc/hz @ 100 hz offset ?122 dbc/hz @ 1 khz offset ?132 dbc/hz @ 10 khz offset ?140 dbc/hz @ 100 khz offset ?146 dbc/hz @ 1 mhz offset ?150 dbc/hz >10 mhz offset ?155 dbc/hz clk-to-cmos additive phase noise distrib ution section only; does not include pll and vco clk = 1 ghz, output = 250 mhz input slew rate > 1 v/ns divider = 4 @ 10 hz offset ?110 dbc/hz @ 100 hz offset ?120 dbc/hz @ 1 khz offset ?127 dbc/hz @ 10 khz offset ?136 dbc/hz @ 100 khz offset ?144 dbc/hz @ 1 mhz offset ?147 dbc/hz >10 mhz offset ?154 dbc/hz
ad9517-1 rev. a | page 9 of 80 parameter min typ max unit test conditions/comments clk = 1 ghz, output = 50 mhz input slew rate > 1 v/ns divider = 20 @ 10 hz offset ?124 dbc/hz @ 100 hz offset ?134 dbc/hz @ 1 khz offset ?142 dbc/hz @ 10 khz offset ?151 dbc/hz @ 100 khz offset ?157 dbc/hz @ 1 mhz offset ?160 dbc/hz >10 mhz offset ?163 dbc/hz clock output absolute phase noise (internal vco used) table 7. parameter min typ max unit test conditions/comments lvpecl absolute phase noise inte rnal vco; direct to lvpecl output vco = 2.65 ghz; output = 2.65 ghz @ 1 khz offset ?46 dbc/hz @ 10 khz offset ?76 dbc/hz @ 100 khz offset ?104 dbc/hz @ 1 mhz offset ?123 dbc/hz @ 10 mhz offset ?140 dbc/hz @ 40 mhz offset ?146 dbc/hz vco = 2.475 ghz; output = 2.45 ghz @ 1 khz offset ?47 dbc/hz @ 10 khz offset ?77 dbc/hz @ 100 khz offset ?105 dbc/hz @ 1 mhz offset ?124 dbc/hz @ 10 mhz offset ?141 dbc/hz @ 40 mhz offset ?146 dbc/hz vco = 2.3 ghz; output = 2.3 ghz @ 1 khz offset ?54 dbc/hz @ 10 khz offset ?78 dbc/hz @ 100 khz offset ?106 dbc/hz @ 1 mhz offset ?125 dbc/hz @ 10 mhz offset ?141 dbc/hz @ 40 mhz offset ?146 dbc/hz
ad9517-1 rev. a | page 10 of 80 clock output absolute time jitter (clock generation using internal vco) table 8. parameter min typ max unit test conditions/comments lvpecl output absolute time jitter application example based on a typical setup where the reference source is clean, so a wider pll loop bandwidth is used; reference = 15.36 mhz; r = 1 vco = 2.46 ghz; lvpecl = 491.52 mhz; pll lbw = 55 khz 142 fs rms integration bw = 200 khz to 10 mhz 370 fs rms integration bw = 12 khz to 20 mhz vco = 2.46 ghz; lvpecl = 122.88 mhz; pll lbw = 55 khz 145 fs rms integration bw = 200 khz to 10 mhz 356 fs rms integration bw = 12 khz to 20 mhz vco = 2.46 ghz; lvpecl = 61.44 mhz; pll lbw = 55 khz 195 fs rms integration bw = 200 khz to 10 mhz 402 fs rms integration bw = 12 khz to 20 mhz clock output absolute time jitter (clock cleanup using internal vco) table 9. parameter min typ max unit test conditions/comments lvpecl output absolute time jitter application example based on a typical setup where the reference source is jittery, so a narrower pll loop bandwidth is used; reference = 10.0 mhz; r = 20 vco = 2.49 ghz; lvpecl = 622.08 mhz; pll lbw = 125 hz 745 fs rms integration bw = 12 khz to 20 mhz vco = 2.49 ghz; lvpecl = 155.52 mhz; pll lbw = 125 hz 712 fs rms integration bw = 12 khz to 20 mhz vco = 2.46 ghz; lvpecl = 122.88 mhz; pll lbw = 125 hz 700 fs rms integration bw = 12 khz to 20 mhz clock output absolute time jitter (clock generation using external vcxo) table 10. parameter min typ max unit test conditions/comments lvpecl output absolute time jitter application example based on a typical setup using an external 245.76 mhz vcxo (toyocom tco-2112); reference = 15.36 mhz; r = 1 lvpecl = 245.76 mhz; pll lbw = 125 hz 54 fs rms integration bw = 200 khz to 5 mhz 77 fs rms integration bw = 200 khz to 10 mhz 109 fs rms integration bw = 12 khz to 20 mhz lvpecl = 122.88 mhz; pll lbw = 125 hz 79 fs rms integration bw = 200 khz to 5 mhz 114 fs rms integration bw = 200 khz to 10 mhz 163 fs rms integration bw = 12 khz to 20 mhz lvpecl = 61.44 mhz; pll lbw = 125 hz 124 fs rms integration bw = 200 khz to 5 mhz 176 fs rms integration bw = 200 khz to 10 mhz 259 fs rms integration bw = 12 khz to 20 mhz
ad9517-1 rev. a | page 11 of 80 clock output additive time jitter (vco divider not used) table 11. parameter min typ max unit test conditions/comments lvpecl output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 622.08 mhz; lvpecl = 622.08 mhz; divider = 1 40 fs rms bw = 12 khz to 20 mhz clk = 622.08 mhz; lvpecl = 155.52 mhz; divider = 4 80 fs rms bw = 12 khz to 20 mhz clk = 1.6 ghz; lvpecl = 100 mhz; divider = 16 215 fs rms calculated from snr of adc method; dcc not used for even divides clk = 500 mhz; lvpecl = 100 mhz; divider = 5 245 fs rms calculated from snr of adc method; dcc on lvds output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 1.6 ghz; lvds = 800 mhz; divider = 2; vco divider not used 85 fs rms bw = 12 khz to 20 mhz clk = 1 ghz; lvds = 200 mhz; divider = 5 113 fs rms bw = 12 khz to 20 mhz clk = 1.6 ghz; lvds = 100 mhz; divider = 16 280 fs rms calculated from snr of adc method; dcc not used for even divides cmos output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 1.6 ghz; cmos = 100 mhz; divider = 16 365 fs rms calculated from snr of adc method; dcc not used for even divides clock output additive time jitter (vco divider used) table 12. parameter min typ max unit test conditions/comments lvpecl output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 2.4 ghz; vco div = 2; lvpecl = 100 mhz; divider = 12; duty-cycle correction = off 210 fs rms calculated from snr of adc method lvds output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 2.4 ghz; vco div = 2; lvds = 100 mhz; divider = 12; duty-cycle correction = off 285 fs rms calculated from snr of adc method cmos output additive time jitter distribution section only; does not include pll and vco; uses rising edge of clock signal clk = 2.4 ghz; vco div = 2; cmos = 100 mhz; divider = 12; duty-cycle correction = off 350 fs rms calculated from snr of adc method
ad9517-1 rev. a | page 12 of 80 delay block additive time jitter table 13. parameter min typ max unit test conditions/comments delay block additive time jitter 1 incremental additive jitter 100 mhz output delay (1600 a, 1c) fine adj. 000000 0.54 ps rms delay (1600 a, 1c) fine adj. 101111 0.60 ps rms delay (800 a, 1c) fine adj. 000000 0.65 ps rms delay (800 a, 1c) fine adj. 101111 0.85 ps rms delay (800 a, 4c) fine adj. 000000 0.79 ps rms delay (800 a, 4c) fine adj. 101111 1.2 ps rms delay (400 a, 4c) fine adj. 000000 1.2 ps rms delay (400 a, 4c) fine adj. 101111 2.0 ps rms delay (200 a, 1c) fine adj. 000000 1.3 ps rms delay (200 a, 1c) fine adj. 101111 2.5 ps rms delay (200 a, 4c) fine adj. 000000 1.9 ps rms delay (200 a, 4c) fine adj. 101111 3.8 ps rms 1 this value is incremental. that is, it is in addition to the jitter of the lvds or cmos output without the delay. to estimate the total jitter, the lvds or cmos output jitter should be added to this value using the root sum of squares (rss) method. serial control port table 14. parameter min typ max unit test conditions/comments cs (input) cs has an internal 30 k pull-up resistor input logic 1 voltage 2.0 v input logic 0 voltage 0.8 v input logic 1 current 3 a input logic 0 current 110 a input capacitance 2 pf sclk (input) sclk has an internal 30 k pull-down resistor input logic 1 voltage 2.0 v input logic 0 voltage 0.8 v input logic 1 current 110 a input logic 0 current 1 a input capacitance 2 pf sdio (when input) input logic 1 voltage 2.0 v input logic 0 voltage 0.8 v input logic 1 current 10 na input logic 0 current 20 na input capacitance 2 pf sdio, sdo (outputs) output logic 1 voltage 2.7 v output logic 0 voltage 0.4 v timing clock rate (sclk, 1/t sclk ) 25 mhz pulse width high, t high 16 ns pulse width low, t low 16 ns sdio to sclk setup, t ds 2 ns sclk to sdio hold, t dh 1.1 ns sclk to valid sdio and sdo, t dv 8 ns cs to sclk setup and hold, t s , t h 2 ns cs minimum pulse width high, t pwh 3 ns
ad9517-1 rev. a | page 13 of 80 pd , sync , and reset pins table 15. parameter min typ max unit test conditions/comments input characteristics these pins each have a 30 k internal pull-up resistor logic 1 voltage 2.0 v logic 0 voltage 0.8 v logic 1 current 110 a logic 0 current 1 a capacitance 2 pf reset timing pulse width low 50 ns sync timing pulse width low 1.5 high speed clock cycles high speed clock is clk input signal ld, status, and refmon pins table 16. parameter min typ max unit test conditions/comments output characteristics when selected as a digital output (cmos); there are other modes in which these pins are not cmos digital outputs; see table 54 , register 0x017, register 0x01a, and register 0x01b output voltage high (v oh ) 2.7 v output voltage low (v ol ) 0.4 v maximum toggle rate 100 mhz applies when mux is set to any divider or counter output or pfd up/down pulse; also applies in analog lock detect mode; usually debug mode only; beware that spurs may couple to output when any of these pins are toggling analog lock detect capacitance 3 pf on-chip capacitance; used to calculate rc time constant for analog lock detect readback; use a pull-up resistor ref1, ref2, and vco frequency status monitor normal range 1.02 mhz frequency above which the monitor indicates the presence of the reference extended range (ref1 and ref2 only) 8 khz frequency above which the monitor indicates the presence of the reference ld pin comparator trip point 1.6 v hysteresis 260 mv
ad9517-1 rev. a | page 14 of 80 power dissipation table 17. parameter min typ max unit test conditions/comments power dissipation, chip power-on default 1.0 1.2 w no clock; no programming; default register values; does not include power dissipated in external resistors full operation; cmos outputs at 206 mhz 1.4 2.0 w pll on; internal vco = 2476 mhz; vco divider = 2; all channel dividers on; six lvpecl outputs @ 619 mhz; eight cmos outputs (10 pf load) @ 206 mhz; all fine delay on, maximum current; does not include power dissipated in external resistors full operation; lvds outputs at 206 mhz 1.4 2.1 w pll on; internal vco = 2476 mhz, vco divider = 2; all channel dividers on; six lvpecl outputs @ 619 mhz; four lvds outputs @ 206 mhz; all fine delay on, maximum current; does not include power di ssipated in external resistors pd power-down 75 185 mw pd pin pulled low; does not include power dissipated in terminations pd power-down, maximum sleep 31 mw pd pin pulled low; pll power-down, register 0x010[1:0] = 01b; sync power-down, register 0x230[2] = 1b; ref for distribution power-down, register 0x230[1] = 1b v cp supply 4 4.8 mw pll operating; typical closed-lo op configuration power deltas, individual functions power delta when a function is enabled/disabled vco divider 30 mw vco divider not used refin (differential) 20 mw all references off to differential reference enabled ref1, ref2 (single-ended) 4 mw all references off to ref1 or ref2 enabled; differential reference not enabled vco 70 mw clk input selected to vco selected pll 75 mw pll off to pll on, normal operation; no reference enabled channel divider 30 mw divider bypassed to divide-by-2 to divide-by-32 lvpecl channel (divider plus output driver) 160 mw no lvpecl output on to one lvpecl output on lvpecl driver 90 mw second lvpecl output turned on, same channel lvds channel (divider plus output driver) 120 mw no lvds output on to one lvds output on lvds driver 50 mw second lvds output turned on, same channel cmos channel (divider plus output driver) 100 mw static; no cmos output on to one cmos output on cmos driver (second in pair) 0 mw static; second cmos output, same pair, turned on cmos driver (first in second pair) 30 mw static; first output, second pair, turned on fine delay block 50 mw delay block off to delay block enabled; maximum current setting
ad9517-1 rev. a | page 15 of 80 timing diagrams cl k t cmos t clk t lvds t pecl 06425-060 differential lvds 80% 20% t rl t fl 06425-062 figure 2. clk/ clk to clock output timing, div = 1 figure 4. lvds timing, differential differential lvpecl 80% 20% t rp t fp 06425-061 single-ended cmos 10pf load 80% 20% t rc t fc 06425-063 figure 3. lvpecl timing, differential figure 5. cmos timing, si ngle-ended, 10 pf load
ad9517-1 rev. a | page 16 of 80 absolute maximum ratings table 18. parameter rating vs, vs_lvpecl to gnd ?0.3 v to +3.6 v vcp to gnd ?0.3 v to +5.8 v refin, refin to gnd ?0.3 v to v s + 0.3 v refin to refin ?3.3 v to +3.3 v rset to gnd ?0.3 v to v s + 0.3 v cprset to gnd ?0.3 v to v s + 0.3 v clk, clk to gnd ?0.3 v to v s + 0.3 v clk to clk ?1.2 v to +1.2 v sclk, sdio, sdo, cs to gnd ?0.3 v to v s + 0.3 v out0, out0 , out1, out1 , out2, out2 , out3, out3 ,out4, out4 , out5, out5 , out6, out6 , out7, out7 to gnd ?0.3 v to v s + 0.3 v sync to gnd ?0.3 v to v s + 0.3 v refmon, status, ld to gnd ?0.3 v to v s + 0.3 v junction temperature 1 150c storage temperature range ?65c to +150c lead temperature (10 sec) 300c 1 see table 19 for ja . stresses above those listed under absolute maximum ratings may cause permanent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. exposure to absolute maximum rating conditions for extended periods may affect device reliability. thermal resistance table 19. package type 1 ja unit 48-lead lfcsp 24.7 c/w 1 thermal impedance measurem ents were taken on a 4- layer board in still air in accordance with eia/jesd51-2. esd caution
ad9517-1 rev. a | page 17 of 80 pin configuration and fu nction descriptions 13 14 15 16 17 18 19 20 21 22 23 24 sclk cs sdo sdio reset pd out2 out2 vs_lvpecl out3 out3 vs 48 47 46 45 44 43 42 41 40 39 38 37 refin (ref1) refin (ref2) cprset vs rset vs out0 out0 vs_lvpecl out1 out1 vs 1 2 3 4 5 6 7 8 9 10 11 12 35 36 34 33 32 31 30 29 28 27 26 25 ad9517-1 top view (not to scale) pin 1 indicator cp status clk vcp refmon ld bypass vs ref_sel lf sync clk out7 (out7a) out5 (out5a) out6 (out6a) out4 (out4a) v s v s vs vs out6 (out6b) out7 (out7b) out5 (out5b) out4 (out4b) 06425-003 notes 1. the external paddle on the bottom of the package must be connected to ground for proper operation. figure 6. pin configuration table 20. pin function descriptions pin no. input/ output pin type mnemonic description 1 i 3.3 v cmos refmon reference monitor (output). this pin has multiple selectable outputs; see table 54 , register 0x01b. 2 o 3.3 v cmos ld lock detect (output). this pin has multiple selectable outputs; see table 54 , register 0x01a. 3 i power vcp power supply for charge pump (cp); v s v cp 5.0 v. 4 o 3.3 v cmos cp charge pump (output). connects to external loop filter. 5 o 3.3 v cmos status status (output). this pin has multiple selectable outputs; see table 54 , register 0x017. 6 i 3.3 v cmos ref_sel reference select. selects ref1 (low) or ref2 (high). this pin has an internal 30 k pull-down resistor. 7 i 3.3 v cmos sync manual synchronizations and manual ho ldover. this pin initiates a manual synchronization and is also used for manual holdover. active low. this pin has an internal 30 k pull-up resistor. 8 i loop filter lf loop filter (input). connects to vco control voltage node internally. this pin has 31 pf of internal capacitance to ground, wh ich may influence the loop filter design for large loop bandwidths. 9 o loop filter bypass this pin is for bypassing the ldo to ground with a capacitor. 10, 24, 25, 30, 31, 36, 37, 43, 45 i power vs 3.3 v power pins. along with clk , this is the self-biased differenti al input for the clock distribution section. 11 i differential clock input clk 12 i differential clock input clk along with clk, this is the self-biased di fferential input for the clock distribution section.
ad9517-1 rev. a | page 18 of 80 pin no. input/ output pin type mnemonic description 13 i 3.3 v cmos sclk serial control port data clock signal. 14 i 3.3 v cmos cs serial control port chip select; active low. this pin has an internal 30 k pull-up resistor. 15 o 3.3 v cmos sdo serial control port unidirectional serial data out. 16 i/o 3.3 v cmos sdio serial control po rt bidirectional serial data in/out. 17 i 3.3 v cmos reset chip reset, active low. this pin has an internal 30 k pull-up resistor. 18 i 3.3 v cmos pd chip power down, active low. this pin has an internal 30 k pull-up resistor. 21, 40 i power vs_lvpecl extended voltage 2.5 v to 3.3 v lvpecl power pins. 42 o lvpecl out0 lvpecl output; one side of a differential lvpecl output. 41 o lvpecl out0 lvpecl output; one side of a differential lvpecl output. 39 o lvpecl out1 lvpecl output; one side of a differential lvpecl output. 38 o lvpecl out1 lvpecl output; one side of a differential lvpecl output. 19 o lvpecl out2 lvpecl output; one side of a differential lvpecl output. 20 o lvpecl out2 lvpecl output; one side of a differential lvpecl output. 22 o lvpecl out3 lvpecl output; one side of a differential lvpecl output. 23 o lvpecl out3 lvpecl output; one side of a differential lvpecl output. 35 o lvds or cmos out4 (out4a) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 34 o lvds or cmos out4 (out4b) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 33 o lvds or cmos out5 (out5a) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 32 o lvds or cmos out5 (out5b) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 26 o lvds or cmos out6 (out6a) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 27 o lvds or cmos out6 (out6b) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 28 o lvds or cmos out7 (out7a) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 29 o lvds or cmos out7 (out7b) lvds/cmos output; one side of a differential lvds output or a single-ended cmos output. 44 o current set resistor rset resistor connected here sets internal bias currents. nominal value = 4.12 k. 46 o current set resistor cprset resistor connected here sets cp current range. nominal value = 5.1 k. 47 i reference input refin (ref2) along with refin, this is the self-b iased differential input for the pll reference. alternatively, this pin is a single-ended input for ref2. 48 i reference input refin (ref1) along with refin , this is the self-biased differenti al input for the pll reference. alternatively, this pin is a single-ended input for ref1. epad gnd gnd ground. the external paddle on the bottom of the package must be connected to ground for proper operation.
ad9517-1 rev. a | page 19 of 80 typical performance characteristics 240 100 120 140 160 180 200 220 0 500 1000 1500 2000 2500 3000 current (ma) frequency (mhz) 2 channels?4 lvpecl 2 channels?2 lvpecl 1 channel?1 lvpecl 06425-007 figure 7. current vs. frequency, direct to output, lvpecl outputs 180 160 140 120 100 80 0 200 400 600 800 current (ma) frequency (mhz) 1 channel?1 lvds 2 channels?2 lvds 2 channels?4 lvds 06425-008 figure 8. current vs. frequencylvds outputs 240 200 160 220 180 140 120 100 80 02 200 150 100 50 current (ma) frequency (mhz) 5 0 1 channel?2 cmos 1 channel?1 cmos 2 channels?2 cmos 2 channels?8 cmos 06425-009 figure 9. current vs. frequencycmos outputs 65 35 40 45 50 55 60 2.3 2.7 2.6 2.5 2.4 k vco (mhz/v) vco frequency (ghz) 06425-010 figure 10. vco k vco vs. frequency 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 0 0.5 1.0 1.5 2.0 2.5 3.0 current from cp pin (ma) voltage on cp pin (v) pump down pump up 06425-011 figure 11. charge pump characteristics @ v cp = 3.3 v 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 0 0.5 1.0 1.5 2.0 3.0 4.0 2.5 3.5 5.04.5 current from cp pin (ma) voltage on cp pin (v) pump down pump up 06425-012 figure 12. charge pump characteristics @ v cp = 5.0 v
ad9517-1 rev. a | page 20 of 80 ? 140 ?145 ?150 ?155 ?160 ?165 ?170 0.1 1 100 10 pfd phase noise referred to pfd input (dbc/hz) pfd frequency (mhz) 06425-013 figure 13. pfd phase noise referred to pfd input vs. pfd frequency ? 210 ?224 ?222 ?220 ?218 ?216 ?214 ?212 02 2.0 1.5 1.0 0.5 pll figure of merit (dbc/hz) slew rate (v/ns) . 5 06425-136 figure 14. pll figure of merit (fom) vs. slew rate at refin/ refin 1.9 1.8 1.7 1.6 1.5 1.4 1.3 1.2 2.3 2.4 2.5 2.6 2.7 vco tuning voltage (v) frequency (ghz) 06425-138 figure 15. vco tuning voltage vs. frequency ?110 ?100 ?90 ?80 ?70 ?60 ?50 ?40 ?30 ?20 ?10 10 0 center 122.88mhz span 50mhz 5mhz/div relative power (db) 06425-137 figure 16. pfd/cp spurs; 122.88 mhz; pfd = 15.36 mhz; lbw = 55 khz; i cp = 4.8 ma; f vco = 2.46 ghz ?110 ?100 ?90 ?80 ?70 ?60 ?50 ?40 ?30 ?20 ?10 10 0 center 122.88mhz span 1mhz 100khz/div relative power (db) 06425-135 figure 17. output spectrum, lvpecl; 122.88 mhz; pfd = 15.36 mhz; lbw = 55 khz; i cp = 4.8 ma; f vco = 2.46 ghz ?110 ?100 ?90 ?80 ?70 ?60 ?50 ?40 ?30 ?20 ?10 10 0 center 122.88mhz span 1mhz 100khz/div relative power (db) 06425-134 figure 18. output spectrum, lvds; 122.88 mhz; pfd = 15.36 mhz; lbw = 55 khz; i cp = 4.8 ma; f vco = 2.46 ghz
ad9517-1 rev. a | page 21 of 80 1.0 0.6 0.2 ?0.2 ?0.6 ?1.0 02 20 15 10 5 differential output (v) time (ns) 5 06425-014 figure 19. lvpecl output (differential) @ 100 mhz 1.0 0.6 0.2 ?0.2 ?0.6 ?1.0 02 1 differential output (v) time (ns) 06425-015 figure 20. lvpecl output (differential) @ 1600 mhz 0.4 0.2 0 ?0.2 ?0.4 02 20 15 10 5 differential output (v) time (ns) 5 06425-016 figure 21. lvds output (differential) @ 100 mhz 0.4 0.2 0 ?0.2 ?0.4 02 1 differential output (v) time (ns) 06425-017 figure 22. lvds output (differential) @ 800 mhz 2.8 0.8 1.8 ?0.2 08 60 100 40 20 output (v) time (ns) 0 06425-018 figure 23.cmos output @ 25 mhz 2.8 0.8 1.8 ?0.2 08 61 10 4 2 output (v) time (ns) 2 06425-019 figure 24. cmos output @ 250 mhz
ad9517-1 rev. a | page 22 of 80 1600 800 1000 1200 1400 03 2 1 differential swing (mv p-p) frequency (ghz) 06425-020 figure 25. lvpecl differential swing vs. frequency 700 500 600 08 700 600 500 400 300 200 100 differential swing (mv p-p) frequency (mhz) 0 0 06425-021 figure 26. lvds differential swing vs. frequency 3 2 1 0 0 600 500 400 300 200 100 output swing (v) output frequency (mhz) c l = 2pf c l = 10pf c l = 20pf 06425-133 figure 27. cmos output swing vs. frequency and capacitive load ? 70 ?80 ?90 ?100 ?110 ?120 ?130 ?140 ?150 10k 100m 10m 1m 100k phase noise (dbc/hz) frequency (hz) 06425-023 figure 28. internal vco phase noise (absolute) direct to lvpecl @ 2650 mhz ? 70 ?80 ?90 ?100 ?110 ?120 ?130 ?140 ?150 10k 100m 10m 1m 100k phase noise (dbc/hz) frequency (hz) 06425-024 figure 29. internal vco phase noise (absolute) direct to lvpecl @ 2475 mhz ? 70 ?80 ?90 ?100 ?110 ?120 ?130 ?140 ?150 10k 100m 10m 1m 100k phase noise (dbc/hz) frequency (hz) 06425-025 figure 30. internal vco phase noise (absolute) direct to lvpecl @ 2300 mhz
ad9517-1 rev. a | page 23 of 80 ? 120 ?130 ?125 ?135 ?140 ?145 ?150 ?155 ?160 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-026 figure 31. phase noise (additive) lvpecl @ 245.76 mhz, divide-by-1 ? 110 ?120 ?130 ?140 ?150 ?160 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-027 figure 32. phase noise (additive) lvpecl @ 200 mhz, divide-by-5 ? 100 ?110 ?120 ?130 ?140 ?150 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-128 figure 33. phase noise (additive) lvpecl @ 1600 mhz, divide-by-1 ? 110 ?160 ?150 ?140 ?130 ?120 10 100m 1k 10k 100k 1m 10m 100 phase noise (dbc/hz) frequency (hz) 06425-142 figure 34. phase noise (additive ) lvds @ 200 mhz, divide-by-1 ? 100 ?110 ?120 ?130 ?140 ?150 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-130 figure 35. phase noise (additive ) lvds @ 800 mhz, divide-by-2 ? 120 ?130 ?140 ?150 ?160 ?170 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-131 figure 36. phase noise (additive ) cmos @ 50 mhz, divide-by-20
ad9517-1 rev. a | page 24 of 80 ? 100 ?110 ?120 ?130 ?140 ?150 ?160 10 100m 10m 1m 100k 10k 1k 100 phase noise (dbc/hz) frequency (hz) 06425-132 figure 37. phase noise (additive ) cmos @ 250 mhz, divide-by-4 ? 120 ?160 ?150 ?140 ?130 1k 100m 10m 1m 100k 10k phase noise (dbc/hz) frequency (hz) 06425-141 figure 38. phase noise (absolute) clock generation; internal vco @ 2.4576 ghz; pfd = 15.36 mhz; lbw = 55 khz; lvpecl output = 122.88 mhz ? 70 ?80 ?90 ?100 ?110 ?120 ?130 ?140 ?150 ?160 1k 100m 10m 1m 100k 10k phase noise (dbc/hz) frequency (hz) 06425-139 figure 39. phase noise (absolute) clock cleanup; internal vco @ 2.488 ghz; pfd = 19.44 mhz; lbw = 12.8 khz; lvpecl output = 155.52 mhz ? 120 ?160 ?150 ?140 ?130 1k 100m 10m 1m 100k 10k phase noise (dbc/hz) frequency (hz) 06425-140 figure 40. phase noise (absolute), external vcxo (toyocom tco-2112) @ 245.76 mhz; pfd = 15.36 mhz; lbw = 250 hz; lvpecl output = 245.76 mhz
ad9517-1 rev. a | page 25 of 80 terminology phase jitter and phase noise an ideal sine wave can be thought of as having a continuous and even progression of phase with time from 0 to 360 for each cycle. actual signals, however, display a certain amount of variation from ideal phase progression over time. this phenomenon is called phase jitter. although many causes can contribute to phase jitter, one major cause is random noise, which is characterized statistically as being gaussian (normal) in distribution. this phase jitter leads to a spreading out of the energy of the sine wave in the frequency domain, producing a continuous power spectrum. this power spectrum is usually reported as a series of values whose units are dbc/hz at a given offset in frequency from the sine wave (carrier). the value is a ratio (expressed in db) of the power contained within a 1 hz bandwidth with respect to the power at the carrier frequency. for each measurement, the offset from the carrier frequency is also given. it is meaningful to integrate the total power contained within some interval of offset frequencies (for example, 10 khz to 10 mhz). this is called the integrated phase noise over that frequency offset interval and can be readily related to the time jitter due to the phase noise within that offset frequency interval. phase noise has a detrimental effect on the performance of adcs, dacs, and rf mixers. it lowers the achievable dynamic range of the converters and mixers, although they are affected in somewhat different ways. time jitter phase noise is a frequency domain phenomenon. in the time domain, the same effect is exhibited as time jitter. when observing a sine wave, the time of successive zero crossings varies. in a square wave, the time jitter is a displacement of the edges from their ideal (regular) times of occurrence. in both cases, the variations in timing from the ideal are the time jitter. because these variations are random in nature, the time jitter is specified in units of seconds root mean square (rms) or 1 sigma of the gaussian distribution. time jitter that occurs on a sampling clock for a dac or an adc decreases the signal-to-noise ratio (snr) and dynamic range of the converter. a sampling clock with the lowest possible jitter provides the highest performance from a given converter. additive phase noise additive phase noise is the amount of phase noise that is attributable to the device or subsystem being measured. the phase noise of any external oscillators or clock sources is subtracted. this makes it possible to predict the degree to which the device impacts the total system phase noise when used in conjunction with the various oscillators and clock sources, each of which contributes its own phase noise to the total. in many cases, the phase noise of one element dominates the system phase noise. when there are multiple contributors to phase noise, the total is the square root of the sum of squares of the individual contributors. additive time jitter additive time jitter is the amount of time jitter that is attributable to the device or subsystem being measured. the time jitter of any external oscillators or clock sources is subtracted. this makes it possible to predict the degree to which the device impacts the total system time jitter when used in conjunction with the various oscillators and clock sources, each of which contributes its own time jitter to the total. in many cases, the time jitter of the external oscillators and clock sources dominates the system time jitter.
ad9517-1 rev. a | page 26 of 80 detailed block diagram programmable n delay refin (ref1) refin (ref2) clk clk ref1 ref2 ad9517-1 status status r divider vco status programmable r delay reference switchover ref_ sel cprset v cp v s gnd rset distribution reference refmon cp status ld p, p + 1 prescaler a/b counters n divider bypass lf low dropout regulator (ldo) vco phase frequency detector lock detect charge pump pll reference hold out0 out1 out0 out1 lvpecl divide by 1 to 32 out2 out3 out2 out3 lvpecl divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 01 divide by 2, 3, 4, 5, or 6 pd sync reset sclk sdio sdo cs digital logic serial control port out4 (out4a) out4 (out4b) out5 (out5a) out5 (out5b) out6 (out6a) out6 (out6b) out7 (out7a) out7 (out7b) t t t t 0 6425-002 figure 41. detailed block diagram
ad9517-1 rev. a | page 27 of 80 theory of operation operational configurations the ad9517 can be configured in several ways. these configurations must be set up by loading the control registers (see table 52 and table 53 through tabl e 62 ). each section or function must be individually programmed by setting the appropriate bits in the corresponding control register or registers. high frequency clock distributionclk or external vco > 1600 mhz the ad9517 power-up default configuration has the pll powered off and the routing of the input set so that the clk/ clk input is connected to the distribution section through the vco divider (divide-by-2/ divide-by-3/divide-by-4/ divide-by-5/divide-by-6). this is a distribution-only mode that allows for an external input up to 2400 mhz (see ). the maximum frequency that can be applied to the channel dividers is 1600 mhz; therefore, higher input frequencies must be divided down before reaching the channel dividers. this input routing can also be used for lower input frequencies, but the minimum divide is 2 before the channel dividers. table 3 when the pll is enabled, this routing also allows the use of the pll with an external vco or vcxo with a frequency of less than 2400 mhz. in this configuration, the internal vco is not used and is powered off. the external vco/vcxo feeds directly into the prescaler. the register settings shown in table 21 are the default values of these registers at power-up or after a reset operation. if the contents of the registers are altered by prior programming after power-up or reset, these registers can also be set intentionally to these values. after the appropriate register values are programmed, register 0x232 must be set to 0x01 for the values to take effect. table 21. default settings of some pll registers register function 0x010[1:0] = 01b pll asynchronous power-down (pll off ). 0x1e0[2:0] = 010b set vco divider = 4. 0x1e1[0] = 0b use the vco divider. 0x1e1[1] = 0b clk selected as the source. when using the internal pll with an external vco, the pll must be turned on. table 22. settings when using an external vco register function 0x010[1:0] = 00b pll normal operation (pll on). 0x010 to 0x01e pll settings. select and enable a reference input; set r, n (p, a, b), pfd polarity, and i cp , according to the intended loop configuration. 0x1e1[1] = 0b clk selected as the source. an external vco requires an external loop filter that must be connected between cp and the tuning pin of the vco. this loop filter determines the loop bandwidth and stability of the pll. make sure to select the proper pfd polarity for the vco being used. table 23. setting the pfd polarity register function 0x010[7] = 0b pfd polarity positive (higher control voltage produces higher frequency). 0x010[7] = 1b pfd polarity negative (higher control voltage produces lower frequency).
ad9517-1 rev. a | page 28 of 80 programmable n delay refin (ref1) refin (ref2) clk clk ref1 ref2 ad9517-1 status status r divider vco status programmable r delay reference switchover ref_ sel cprset v cp v s gnd rset distribution reference refmon cp status ld p, p + 1 prescaler a/b counters n divider bypass lf low dropout regulator (ldo) vco phase frequency detector lock detect charge pump pll reference hold out0 out1 out0 out1 lvpecl divide by 1 to 32 out2 out3 out2 out3 lvpecl divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 01 divide by 2, 3, 4, 5, or 6 pd sync reset sclk sdio sdo cs digital logic serial control port out4 (out4a) out4 (out4b) out5 (out5a) out5 (out5b) out6 (out6a) out6 (out6b) out7 (out7a) out7 (out7b) t t t t 06425-029 figure 42. high frequency clock distribution or external vco >1600 mhz
ad9517-1 rev. a | page 29 of 80 programmable n delay refin (ref1) refin (ref2) clk clk ref1 ref2 ad9517-1 status status r divider vco status programmable r delay reference switchover ref_ sel cprset v cp v s gnd rset distribution reference refmon cp status ld p, p + 1 prescaler a/b counters n divider bypass lf low dropout regulator (ldo) vco phase frequency detector lock detect charge pump pll reference hold out0 out1 out0 out1 lvpecl divide by 1 to 32 out2 out3 out2 out3 lvpecl divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 01 divide by 2, 3, 4, 5, or 6 pd sync reset sclk sdio sdo cs digital logic serial control port out4 (out4a) out4 (out4b) out5 (out5a) out5 (out5b) out6 (out6a) out6 (out6b) out7 (out7a) out7 (out7b) t t t t 06425-030 figure 43. internal vco and clock distribution internal vco and clock distribution when using the internal vco and pll, the vco divider must be employed to ensure that the frequency presented to the channel dividers does not exceed its specified maximum frequency (1600 mhz, see table 3 ). the internal pll uses an external loop filter to set the loop bandwidth. the external loop filter is also crucial to the loop stability. when using the internal vco, it is necessary to calibrate the vco (register 0x018[0]) to ensure optimal performance. for internal vco and clock distribution applications, the register settings shown in table 24 should be used. table 24. settings when using internal vco register function 0x010[1:0] = 00b pll normal operation (pll on). 0x010 to 0x1e pll settings. select and enable a reference input; set r, n (p, a, b), pfd polarity, and i cp according to the intended loop configuration. 0x018[0] = 0, 0x232[0] = 1 reset vco calibration (this does not have to be done first time after power-up, but must be done subsequently). 0x1e0[2:0] vco divider set to divide-by-2, divide-by-3, divide-by-4, divide-by-5, and divide-by-6. 0x1e1[0] = 0b use the vco divider as source for distribution section. 0x1e1[1] = 1b vco selected as the source. 0x018[0] = 1, 0x232[0] = 1 initiate vco calibration.
ad9517-1 rev. a | page 30 of 80 programmable n delay refin (ref1) refin (ref2) clk clk ref1 ref2 ad9517-1 status status r divider vco status programmable r delay reference switchover ref_ sel cprset v cp v s gnd rset distribution reference refmon cp status ld p, p + 1 prescaler a/b counters n divider bypass lf low dropout regulator (ldo) vco phase frequency detector lock detect charge pump pll reference hold out0 out1 out0 out1 lvpecl divide by 1 to 32 out2 out3 out2 out3 lvpecl divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 divide by 1 to 32 lvds/cmos divide by 1 to 32 01 pd sync reset sclk sdio sdo cs digital logic serial control port out4 (out4a) out4 (out4b) out5 (out5a) out5 (out5b) out6 (out6a) out6 (out6b) out7 (out7a) out7 (out7b) divide by 2, 3, 4, 5, or 6 t t t t 06425-028 figure 44. clock distribution or external vco < 1600 mhz
ad9517-1 rev. a | page 31 of 80 clock distribution or external vco < 1600 mhz when the external clock source to be distributed or the external vco/vcxo is <1600 mhz, a configuration that bypasses the vco divider can be used. this differs from the high frequency clock distributionclk or external vco > 1600 mhz section only in that the vco divider (divide-by-2, divide-by-3, divide- by-4, divide-by-5, and divide-by-6) is bypassed. this limits the frequency of the clock source to <1600 mhz (due to the maximum input frequency allowed at the channel dividers). configuration and register settings for clock distribution applications where the external clock is <1600 mhz, the register settings shown in table 25 should be used. table 25. settings for clock distribution < 1600 mhz register function 0x010[1:0] = 01b pll asynchronous power-down (pll off ) 0x1e1[0] = 1b bypass the vco divider as source for distribution section 0x1e1[1] = 0b clk selected as the source when using the internal pll with an external vco < 1600 mhz, the pll must be turned on. table 26. settings for using internal pll with external vco < 1600 mhz register function 0x1e1[0] = 1b bypass the vco divider as source for distribution section 0x010[1:0] = 00b pll normal operation (pll on) along with other appropriate pll settings in 0x10 to 0x1e an external vco/vcxo requires an external loop filter that must be connected between cp and the tuning pin of the vco/vcxo. this loop filter determines the loop bandwidth and stability of the pll. make sure to select the proper pfd polarity for the vco/vcxo being used. table 27. setting the pfd polarity register function 0x010[7] = 0 pfd polarity positive (higher control voltage produces higher frequency) 0x010[7] = 1 pfd polarity negative (higher control voltage produces lower frequency) after the appropriate register values are programmed, register 0x232 must be set to 0x01 for the values to take effect.
ad9517-1 rev. a | page 32 of 80 phase-locked loop (pll) clk charge pump r divider cp v cp v sgnd status cprset dist ref rset divide by 2, 3, 4, 5, or 6 a/b counters ld n divider refmon lf bypass low dropout regulator (ldo) 01 0 1 vco p, p + 1 prescaler ref2 ref1 reference switchover hold vco status ref_sel lock detect status status clk phase frequency detector programmable n delay programmable r delay pll ref refin (ref1) refin (ref2) 06425-064 figure 45. pll functional blocks the ad9517 includes an on-chip pll with an on-chip vco. the pll blocks can be used either with the on-chip vco to create a complete phase-locked loop, or with an external vco or vcxo. the pll requires an external loop filter, which usually consists of a small number of capacitors and resistors. the configuration and components of the loop filter help to establish the loop bandwidth and stability of the operating pll. the ad9517 pll is useful for generating clock frequencies from a supplied reference frequency. this includes conversion of reference frequencies to much higher frequencies for subsequent division and distribution. in addition, the pll can be exploited to clean up jitter and phase noise on a noisy reference. the exact choices of pll parameters and loop dynamics are application specific. the flexibility and depth of the ad9517 pll allow the part to be tailored to function in many different applications and signal environments. configuration of the pll the ad9517 allows flexible configuration of the pll, accommodating various reference frequencies, pfd comparison frequencies, vco frequencies, internal or external vco/vcxo, and loop dynamics. this is accomplished by the various settings that include the r divider, the n divider, the pfd polarity (only applicable to external vco/vcxo), the antibacklash pulse width, the charge pump current, the selection of internal vco or external vco/vcxo, and the loop bandwidth. these are managed through programmable register settings (see table 52 and table 54 ) and by the design of the external loop filter. successful pll operation and satisfactory pll loop performance are highly dependent upon proper configuration of the pll settings. the design of the external loop filter is crucial to the proper operation of the pll. a thorough knowledge of pll theory and design is helpful. adisimclk ? (v1.2 or later) is a free program that can help with the design and exploration of the capabilities and features of the ad9517, including the design of the pll loop filter. it is available at www.analog.com/clocks . phase frequency detector (pfd) the pfd takes inputs from the r counter and n counter and produces an output proportional to the phase and frequency difference between them. the pfd includes a programmable delay element that controls the width of the antibacklash pulse. this pulse ensures that there is no dead zone in the pfd transfer function and minimizes phase noise and reference spurs. the antibacklash pulse width is set by register 0x017[1:0]. an important limit to keep in mind is the maximum frequency allowed into the pfd, which in turn determines the correct antibacklash pulse setting. the antibacklash pulse setting is specified in the phase/frequency detector parameter of table 2 .
ad9517-1 rev. a | page 33 of 80 charge pump (cp) the charge pump is controlled by the pfd. the pfd monitors the phase and frequency relationship between its two inputs and tells the cp to pump up or pump down to charge or discharge the integrating node (part of the loop filter). the integrated and filtered cp current is transformed into a voltage that drives the tuning node of the internal vco through the lf pin (or the tuning pin of an external vco) to move the vco frequency up or down. the cp can be set (register 0x010[6:4]) for high impedance (allows holdover operation), for normal operation (attempts to lock the pll loop), for pump up, or for pump down (test modes). the cp current is programmable in eight steps from (nominally) 600 a to 4.8 ma. the exact value of the cp current lsb is set by the cp_rset resistor, which is nominally 5.1 k. if the value of the cp_rset is doubled, the resulting charge pump current range becomes 300 a to 2.4 ma. on-chip vco the ad9517 includes an on-chip vco covering the frequency range shown in table 2 . achieving low vco phase noise was a priority in the design of the vco. to tune over the wide range of frequencies covered by this vco, ranges are used. this is largely transparent to the user but is the reason that the vco must be calibrated when the pll loop is first set up. the calibration procedure ensures that the vco operating voltage is centered for the desired vco frequency. see the vco calibration section for additional information. the on-chip vco is powered by an on-chip, low drop out (ldo), linear voltage regulator. the ldo provides some isolation of the vco from variations in the power supply voltage level. the bypass pin should be connected to ground by a 220 nf capacitor to ensure stability. this ldo employs the same technology used in the anycap? line of regulators from analog devices, inc., making it insensitive to the type of capacitor used. driving an external load from the bypass pin is not supported. note that the reference input signal must be present and the vco divider must not be static during vco calibration. pll external loop filter when using the internal vco, the external loop filter should be referenced to the bypass pin for optimal noise and spurious performance. an example of an external loop filter for a pll that uses the internal vco is shown in figure 46 . the third- order design shown in figure 46 usually offers the best performance. a loop filter must be calculated for each desired pll configuration. the values of the components depend upon the vco frequency, the k vco , the pfd frequency, the cp current, the desired loop bandwidth, and the desired phase margin. the loop filter affects the phase noise, the loop settling time, and the loop stability. a basic knowledge of pll theory is helpful for under- standing loop filter design. adisimclk can help with the calculation of a loop filter according to the application requirements. when using an external vco, the external loop filter should be referenced to ground. an example of an external loop filter for a pll using an external vco is shown in figure 47 . lf vco charge pump cp bypass c1 c2 c3 r1 31pf r2 c bp = 220nf ad9517-1 06425-065 figure 46. example of external loop filter for a pll using the internal vco clk/clk external vco/vcxo charge pump cp c1 c2 c3 r1 r2 ad9517-1 06425-265 figure 47. example of external loop filter for a pll using an external vco pll reference inputs the ad9517 features a flexible pll reference input circuit that allows either a fully differential input or two separate single- ended inputs. the input frequency range for the reference inputs is specified in table 2 . both the differential and the single-ended inputs are self-biased, allowing for easy ac coupling of input signals. the differential input and the single-ended inputs share the two pins, refin (ref1)/ refin (ref2). the desired reference input type is selected and controlled by register 0x01c (see and ). table 52 table 54 when the differential reference input is selected, the self-bias level of the two sides is offset slightly (~100 mv, see table 2 ) to prevent chattering of the input buffer when the reference is slow or missing. this increases the voltage swing required of the driver and overcomes the offset. the differential reference input can be driven by either ac-coupled lvds or ac-coupled lvpecl signals. the single-ended inputs can be driven by either a dc-coupled cmos level signal or an ac-coupled sine wave or square wave. each single-ended input can be independently powered down when not needed to increase isolation and reduce power. either a differential or a single-ended reference must be specifically enabled. all pll reference inputs are off by default. the differential reference input is powered down whenever the pll is powered down or when the differential reference input is not selected. the single-ended buffers power down when the pll is powered down and when their individual power-down registers are set. when the differential mode is selected, the single-ended inputs are powered down.
ad9517-1 rev. a | page 34 of 80 in differential mode, the reference input pins are internally self- biased so that they can be ac-coupled via capacitors. it is possible to dc couple to these inputs. if the differential refin is driven by a single-ended signal, the unused side ( refin ) should be decoupled via a suitable capacitor to a quiet ground. shows the equivalent circuit of refin. figure 48 v s ref1 ref2 refin 150? 150? 10k ? 12k ? 10k ? 10k ? refin 85k ? v s 85k ? v s 06425-066 figure 48. refin eq uivalent circuit reference switchover the ad9517 supports dual single-ended cmos inputs, as well as a single differential reference input. in the dual single-ended reference mode, the ad9517 supports automatic and manual pll reference clock switching between ref1 (on pin refin) and ref2 (on pin refin ). this feature supports networking and other applications that require hitless switching of redundant references. when used in conjunction with the automatic holdover function, the ad9517 can achieve a worst-case reference input switchover with an output frequency disturbance as low as 10 ppm. when using reference switchover, the single-ended reference inputs should be dc-coupled cmos levels and never be allowed to go to high impedance. if these inputs are allowed to go to high impedance, noise may cause the buffer to chatter, causing a false detection of the presence of a reference. t here are several configurable modes of reference switchover. the switchover can be performed manually or automatically. manual switchover is performed either through register 0x01c or by using the ref_sel pin. the automatic switchover occurs when ref1 disappears. a switchover deglitch feature ensures that the pll does not receive rising edges that are far out of alignment with the newly selected reference. t here are two automatic reference switchover modes, as follows, that are set in register 0x01c: ? prefer ref1. switch from ref1 to ref2 when ref1 disappears. return to ref1 from ref2 when ref1 returns. ? stay on ref2. automatically switch to ref2 if ref1 disappears but do not switch back to ref1 if it reappears. the reference can be set back to ref1 manually at an appropriate time. in automatic mode, ref1 is monitored by ref2. if ref1 disappears (two consecutive falling edges of ref2 without an edge transition on ref1), ref1 is considered missing. on the next subsequent rising edge of ref2, ref2 is used as the reference clock to the pll. if register 0x01c[3] = 0b (default), when ref1 returns (four rising edges of ref1 without two falling edges of ref2 between the ref1 edges), the pll reference switches back to ref1. if register 0x01c[3] = 1b, the user can control when to switch back to ref1. this is done by programming the part to manual reference select mode (register 0x01c[4] = 0b) and by ensuring that the registers and/or the ref_sel pin are set to select the desired reference. automatic mode can be reactivated when ref1 is reselected. manual switchover requires the presence of a clock on the reference input being switched to or that the deglitching feature be disabled (register 0x01c[7]). reference divider r the reference inputs are routed to the reference divider, r. r (a 14-bit counter) can be set to any value from 0 to 16383 by writing to register 0x011 and register 0x012. (both r = 0 and r = 1 give divide-by-1.) the output of the r divider goes to one of the pfd inputs to be compared with the vco frequency divided by the n divider. the frequency applied to the pfd must not exceed the maximum allowable frequency, which depends on the antibacklash pulse setting (see table 2 ). the r counter has its own reset. r counter can be reset using the shared reset bit of the r, a, and b counters. it can also be reset by a sync operation. vcxo/vco feedback divider np, a, b, r the n divider is a combination of a prescaler (p) and two counters, a and b. the total divider value is n = ( p b ) + a where p can be 2, 4, 8, 16, or 32. prescaler the prescaler of the ad9517 allows for two modes of operation: a fixed divide (fd) mode of 1, 2, or 3, and a dual modulus (dm) mode where the prescaler divides by p and (p + 1) {2 and 3, 4 and 5, 8 and 9, 16 and 17, or 32 and 33}. the prescaler modes of operation are given in table 54 , register 0x16[2:0]. not all modes are available at all frequencies (see tabl e 2 ). when operating the ad9517 in dual modulus mode (p//p + 1), the equation used to relate input reference frequency to vco output frequency is f vco = ( f ref / r ) ( p b + a ) = f ref n / r
ad9517-1 rev. a | page 35 of 80 however, when operating the prescaler in fd mode 1, 2, or 3, the a counter is not used (a = 0) and the equation simplifies to f vco = ( f ref / r ) ( p b ) = f ref n / r when a = 0, the divide is a fixed divide of p = 2, 4, 8, 16, or 32, in which case the previous equation also applies. by using combinations of dm and fd modes, the ad9517 can achieve values of n all the way down to n = 1 and up to n = 26,2175. table 2 8 shows how a 10 mhz reference input can be locked to any integer multiple of n. note that the same value of n can be derived in different ways, as illustrated by the case of n = 12. the user can choose a fixed divide mode p = 2 with b = 6, use the dual modulus mode 2/3 with a = 0, b = 6, or use the dual modulus mode 4/5 with a = 0, b = 3. a and b counters the b counter must be 3 or bypassed, and, unlike the r counter, a = 0 is actually zero. when the prescaler is in dual-modulus mode, the a counter must be less than the b counter. the maximum input frequency to the a/b counter is reflected in the maximum prescaler output frequency (~300 mhz) that is specified in tabl e 2 . this is the prescaler input frequency (vco or clk) divided by p. for example, dual modulus p = 8/9 mode is not allowed if the vco frequency is greater than 2400 mhz because the frequency going to the a/b counter is too high. when the ad9517 b counter is bypassed (b = 1), the a counter should be set to 0, and the overall resulting divide is equal to the prescaler setting, p. the possible divide ratios in this mode are 1, 2, 3, 4, 8, 16, and 32. this mode is useful only when an external vco/vcxo is used because the frequency range of the internal vco requires an overall feedback divider greater than 32. although manual reset is not normally required, the a/b counters have their own reset bit. alternatively, the a and b counters can be reset using the shared reset bit of the r, a, and b counters. note that these reset bits are not self-clearing. r, a, and b counters sync pin reset the r, a, and b counters can also be reset simultaneously through the sync pin. this function is controlled by register 0x019[7:6] (see ). the table 54 sync pin reset is disabled by default. r and n divider delays both the r and n dividers feature a programmable delay cell. these delays can be enabled to allow adjustment of the phase relationship between the pll reference clock and the vco or clk. each delay is controlled by three bits. the total delay range is about 1 ns. see register 0x019 in table 54 . table 28. using a 10 mhz reference input to generate different vco frequencies f ref (mhz) r p a b n f vco (mhz) mode comments/conditions 10 1 1 x 1 1 10 fd p = 1, b = 1 (a and b counters are bypassed). 10 1 2 x 1 2 20 fd p = 2, b = 1 (a and b counters are bypassed). 10 1 1 x 3 3 30 fd a counter is bypassed. 10 1 1 x 4 4 40 fd a counter is bypassed. 10 1 1 x 5 5 50 fd a counter is bypassed. 10 1 2 x 3 6 60 fd a counter is bypassed. 10 1 2 0 3 6 60 dm 10 1 2 1 3 7 70 dm 10 1 2 2 3 8 80 dm 10 1 2 1 4 9 90 dm 10 1 8 6 18 150 1500 dm 10 1 8 7 18 151 1510 dm 10 1 16 7 9 151 1510 dm 10 10 32 6 47 1510 1510 dm 10 1 8 0 25 200 2000 dm 10 1 16 14 16 270 2700 dm p = 8 is not allowed (2700 8 > 300 mhz). p = 32 is not allowed (a > b not allowed). 10 10 32 22 84 2710 2710 dm p = 32, a = 22, b = 84. p = 16 is also permitted.
ad9517-1 rev. a | page 36 of 80 digital lock detect (dld) by selecting the proper output through the mux on each pin, the dld function can be made available at the ld, status, and refmon pins. the dld circuit indicates a lock when the time difference of the rising edges at the pfd inputs is less than a specified value (the lock threshold). the loss of a lock is indicated when the time difference exceeds a specified value (the unlock threshold). note that the unlock threshold is wider than the lock threshold, which allows some phase error in excess of the lock window to occur without chattering on the lock indicator. the lock detect window timing depends on three settings: the digital lock detect window bit (register 0x018[4]), the antibacklash pulse width setting (register 0x017[1:0], see table 2 ), and the lock detect counter (register 0x018[6:5]). a lock is not indicated until there is a programmable number of consecutive pfd cycles with a time difference that is less than the lock detect threshold. the lock detect circuit continues to indicate a lock until a time difference greater than the unlock threshold occurs on a single subsequent cycle. for the lock detect to work properly, the period of the pfd frequency must be greater than the unlock threshold. the number of consecutive pfd cycles required for lock is programmable (register 0x018[6:5]). a nalog lock detect (ald) t he ad9517 provides an ald function that can be selected for use at the ld pin. there are two versions of ald, as follows: ? n-channel open-drain lock detect. this signal requires a pull-up resistor to the positive supply, vs. the output is normally high with short, low-going pulses. lock is indicated by the minimum duty cycle of the low-going pulses. ? p-channel open-drain lock detect. this signal requires a pull-down resistor to gnd. the output is normally low with short, high-going pulses. lock is indicated by the minimum duty cycle of the high-going pulses. the analog lock detect function requires an r-c filter to provide a logic level indicating lock/unlock. ad9517-1 ald ld r1 c v out r2 v s = 3.3 v 06425-067 figure 49. example of analog lock detect filter using an n-channel open-drain driver current source digital lock detect (dld) during the pll locking sequence, it is normal for the dld signal to toggle a number of times before remaining steady when the pll is completely locked and stable. there may be applications where it is desirable to have dld asserted only after the pll is solidly locked. this made is possible by using the current source lock detect function. the current source lock detect function is set when it is selected as the output from the ld pin control (register 0x01a[5:0]). the current source lock detect provides a current of 110 a when dld is true, and it shorts to ground when dld is false. if a capacitor is connected to the ld pin, it charges at a rate that is determined by the current source during the dld true time but is discharged nearly instantly when dld is false. by monitoring the voltage at the ld pin (top of the capacitor), it is possible to get a logic high level only after the dld has been true for a sufficiently long time. any momentary dld false resets the charging. by selecting a properly sized capacitor, it is possible to delay a lock detect indication until the pll is stably locked and the lock detect does not chatter. the voltage on the capacitor can be sensed by an external comparator connected to the ld pin. however, there is an internal ld pin comparator that can be read at the refmon pin control (register 0x01b[4:0]) or the status pin control (register 0x017[7:2]) as an active high signal. it is also available as an active low signal (refmon, register 0x01b[4:0] and status, register 0x017[7:2]). the internal ld pin comparator trip point and hysteresis are listed in table 16 . ad9517-1 ld refmon or status c v out 110a dld ld pin comparator 06425-068 figure 50. current source lock detect external vcxo/vco clock input (clk/ clk ) clk is a differential input that can be used as an input to drive the ad9517 clock distribution section. this input can receive up to 2.4 ghz. the pins are internally self-biased, and the input signal should be ac-coupled via capacitors. v s clock input stage c lk c lk 5k? 5k? 2.5k ? 2.5k ? 06425-032 figure 51. clk equivalent input circuit the clk/ clk input can be used either as a distribution-only input (with the pll off), or as a feedback input for an external vco/vcxo using the internal pll when the internal vco is not used. the clk/ clk input can be used for frequencies up to 2.4 ghz.
ad9517-1 rev. a | page 37 of 80 holdover the ad9517 pll has a holdover function. holdover is implemented by putting the charge pump into a high impedance state. this is useful when the pll reference clock is lost. holdover mode allows the vco to maintain a relatively constant frequency even though there is no reference clock. without this function, the charge pump is placed into a constant pump-up or pump-down state, resulting in a massive vco frequency shift. because the charge pump is placed in a high impedance state, any leakage that occurs at the charge pump output or the vco tuning node causes a drift of the vco frequency. this can be mitigated by using a loop filter that contains a large capacitive component because this drift is limited by the current leakage induced slew rate (i leak /c) of the vco control voltage. for most applications, the frequency accuracy is sufficient for 3 sec to 5 sec. both a manual holdover, using the sync pin, and an automatic holdover mode are provided. to use either function, the holdover function must be enabled (register 0x01d[0] and register 0x01d[2]). note that the vco cannot be calibrated with the holdover enabled because the holdover resets the n divider during calibration, which prevents proper calibration. disable holdover before issuing a vco calibration. manual holdover mode a manual holdover mode can be enabled that allows the user to place the charge pump into a high impedance state when the sync pin is asserted low. this operation is edge sensitive, not level sensitive. the charge pump enters a high impedance state immediately. to take the charge pump out of a high impedance state, take the sync pin high. the charge pump then leaves high impedance state synchronously with the next pfd rising edge from the reference clock. this prevents extraneous charge pump events from occurring during the time between sync going high and the next pfd event. this also means that the charge pump stays in a high impedance state as long as there is no reference clock present. the b-counter (in the n divider) is reset synchronously with the charge pump leaving the high impedance state on the reference path pfd event. this helps align the edges out of the r and n dividers for faster settling of the pll. because the prescaler is not reset, this feature works best when the b and r numbers are close because this results in a smaller phase difference for the loop to settle out. when using this mode, set the channel dividers to ignore the sync pin (at least after an initial sync event). if the dividers are not set to ignore the sync pin, each time sync is taken low to put the part into holdover, the distribution outputs turn off. automatic/internal holdover mode when enabled, this function automatically puts the charge pump into a high impedance state when the loop loses lock. the assumption is that the only reason the loop loses lock is due to the pll losing the reference clock; therefore, the holdover function puts the charge pump into a high impedance state to maintain the vco frequency as close as possible to the original frequency before the reference clock disappears. a flowchart of the internal/ automatic holdover function operation is shown in figure 52 . no no no no yes yes yes yes yes pll enabled dld == low was ld pin == high when dld went low? high impedance charge pump reference edge at pfd? release charge pump high impedance dld == high loop out of lock. digital lock detect signal goes low when the loop leaves lock as determined by the phase difference at the input of the pfd. analog lock detect pin indicates lock was previously achieved. (0x1d[3] = 1: use ld pin voltage with holdover. 0x1d[3] = 0: ignore ld pin voltage, treat ld pin as always high.) charge pump is made high impedance. pll counters continue operating normally. charge pump remains high impedance until the reference has returned. take charge pump out of high impedance. pll can now resettle. wait for dld to go high. this takes 5 to 255 cycles (programming of the dld delay counter) with the reference and feedback clocks inside the lock window at the pfd. this ensures that the holdover function waits for the pll to settle and lock before the holdover function can be retriggered. yes 06425-069 figure 52. flow chart of auto matic/internal holdover mode the holdover function senses the logic level of the ld pin as a condition to enter holdover. the signal at ld can be from the dld, ald, or current source ld mode. it is possible to disable the ld comparator (register 0x01d[3]), which causes the holdover function to always sense ld as high.
ad9517-1 rev. a | page 38 of 80 if dld is used, it is possible for the dld signal to chatter some while the pll is reacquiring lock. the holdover function may retrigger, thereby preventing the holdover mode from terminating. use of the current source lock detect mode is recommended to avoid this situation (see the current source digital lock detect section). once in holdover mode, the charge pump stays in a high impedance state as long as there is no reference clock present. as in the external holdover mode, the b counter (in the n divider) is reset synchronously with the charge pump leaving the high impedance state on the reference path pfd event. this helps align the edges out of the r and n dividers for faster settling of the pll and to reduce frequency errors during settling. because the prescaler is not reset, this feature works best when the b and r numbers are close because this results in a smaller phase difference for the loop to settle out. after leaving holdover, the loop then reacquires lock and the ld pin must charge (if register 0x01d[3] = 1) before it can re-enter holdover (cp high impedance). t he holdover function always responds to the state of the currently selected reference (register 0x01c). if the loop loses lock during a reference switchover (see the reference switchover section), holdover is triggered briefly until the next reference clock edge at the pfd. t he following registers affect the internal/automatic holdover function: ? register 0x018[6:5]. lock detect counter. this changes how many consecutive pfd cycles with edges inside the lock detect window are required for the dld indicator to indicate lock. this impacts the time required before the ld pin can begin to charge as well as the delay from the end of a holdover event until the holdover function can be re-engaged. ? register 0x018[3]. disable digital lock detect. this bit must be set to a 0 to enable the dld circuit. internal/automatic holdover does not operate correctly without the dld function enabled. ? register 0x01a[5:0]. lock detect pin output select. set this to 000100b to put it in the current source lock detect mode if using the ld pin comparator. load the ld pin with a capacitor of an appropriate value. ? register 0x01d[3]. enable ld pin comparator; 1 = enable; 0 = disable. when disabled, the holdover function always senses the ld pin as high. ? register 0x01d[1]. enable external holdover control. ? register 0x01d[0] and register 0x01d[2]. holdover function enable. if holdover is disabled, both external and internal/automatic holdover are disabled. f or example, to use automatic holdover with the following: ? automatic reference switchover, prefer ref1 ? digital lock detect: five pfd cycles, high range window ? automatic holdover using the ld pin comparator s et the following registers (in addition to the normal pll registers): ? register 0x018[6:5] = 00b; lock detect counter = five cycles. ? register 0x018[4] = 0b; lock detect window = high range. ? register 0x018[3] = 0b; dld normal operation. ? register 0x01a[5:0] = 000100b; current source lock detect mode. ? register 0x01c[4] = 1b; automatic reference switchover enabled. ? register 0x01c[3] = 0b; prefer ref1. ? register 0x01c[2:1] = 11b; enable ref1 and ref2 input buffers. ? register 0x01d[3] = 1b; enable ld pin comparator. ? register 0x01d[2]=1b; enable the holdover function. ? register 0x01d[1] = 0b; use internal/automatic holdover mode. ? register 0x01d[0] = 1b; enable the holdover function. frequency status monitors the ad9517 contains three frequency status monitors that are used to indicate if the pll reference (or references in the case of single-ended mode) and the vco have fallen below a threshold frequency. a diagram showing their location in the pll is shown in figure 53 . the pll reference monitors have two threshold frequencies: normal and extended (see tabl e 16 ). the reference frequency monitor thresholds are selected in register 0x01f.
ad9517-1 rev. a | page 39 of 80 programmable n delay refin (ref1) refin (ref2) clk clk ref1 ref2 status status r divider vco status programmable r delay reference switchover ref_sel cprset v cp v s gnd rset distribution reference refmon cp status ld p, p + 1 prescaler a/b counters n divider bypass lf low dropout regulator (ldo) vco phase frequency detector lock detect charge pump pll reference hold 01 0 1 divide by 2, 3, 4, 5, or 6 06425-070 figure 53. reference and vco status monitors vco calibration t he ad9517 on-chip vco must be calibrated to ensure proper operation over process and temperature. the vco calibration is controlled by a calibration controller running off of a divided refin clock. the calibration requires that the pll be set up properly to lock the pll loop and that the refin clock be present. during the first initialization after a power-up or a reset of the ad9517, a vco calibration sequence is initiated by setting register 0x018[0] = 1b. this can be done as part of the initial setup before executing update registers (register 0x232[0] = 1b). subsequent to the initial setup, a vco calibration sequence is initiated by resetting register 0x018[0] = 0b, executing an update registers operation, setting register 0x018[0] = 1b, and executing another update registers operation. the readback bit (register 0x1f[6]) indicates when a vco calibration is finished by returning a logic true (that is, 1b). t he sequence of operations for the vco calibration is: ? program the pll registers to the proper values for the pll loop. note that that automatic holdover mode must be disabled, and the vco divider must not be set to static. ? ensure that the input reference signal is present. ? for the initial setting of the registers after a power-up or reset, initiate vco calibration by setting register 0x018[0] = 1b. subsequently, whenever a calibration is desired, set register 0x018[0] = 0b, update registers; and set register 0x018[0] = 1b, update registers. ? a sync operation is initiated internally, causing the outputs to go to a static state determined by normal sync function operation. ? vco calibrates to the desired setting for the requested vco frequency. ? internally, the sync signal is released, allowing outputs to continue clocking. ? pll loop is closed. ? pll locks. a sync is executed during the vco calibration; therefore, the outputs of the ad9517 are held static during the calibration, which prevents unwanted frequencies from being produced. however, at the end of a vco calibration, the outputs may resume clocking before the pll loop is completely settled. the vco calibration clock divider is set as shown in table 54 (register 0x018[2:1]). the calibration divider divides the pfd frequency (reference frequency divided by r) down to the calibration clock. the calibration occurs at the pfd frequency divided by the calibration divider setting. lower vco calibration clock frequencies result in longer times for a calibration to be completed. the vco calibration clock frequency is given by f cal_clock = f refin /( r cal_div ) where: f refin is the frequency of the refin signal. r is the value of the r divider. cal_div is the division set for the vco calibration divider (register 0x018[2:1]). the vco calibration takes 4400 calibration clock cycles. therefore, the vco calibration time in pll reference clock cycles is given by time to calibrate vco = 4400 r cal_div pll reference clock cycles table . eample time to complete a vco calibration with different f refin freuencies f refin mh r divider pfd time to calibrate vco 100 1 100 mhz 88 s 10 10 1 mhz 8.8 ms 10 100 100 khz 88 ms
ad9517-1 rev. a | page 40 of 80 v co calibration must be manually initiated. this allows for flexibility in deciding what order to program registers and when to initiate a calibration, instead of having it happen every time certain pll registers have their values change. for example, this allows for the vco frequency to be changed by small amounts without having an automatic calibration occur each time; this should be done with caution and only when the user knows the vco control voltage is not going to exceed the nominal best performance limits. for example, a few 100 khz steps are fine, but a few mhz might not be. in addition, because the calibration procedure results in rapid changes in the vco frequency, the distribution section is automatically placed in sync until the calibration is finished. therefore, this temporary loss of outputs must be expected. a vco calibration should be initiated under the following conditions: ? after changing any of the pll r, p, b, and a divider settings, or after a change in the pll reference clock frequency. this, in effect, means any time a pll register or reference clock is changed such that a different vco frequency results. ? whenever system calibration is desired. the vco is designed to operate properly over extremes of temperatures even when it is first calibrated at the opposite extreme. however, a vco calibration can be initiated at any time, if desired. clock distribution a clock channel consists of a pair (or double pair, in the case of cmos) of outputs that share a common divider. a clock output consists of the drivers that connect to the output pins. the clock outputs have either lvpecl or lvds/cmos signal levels at the pins. the ad9517 has four clock channels: two channels are lvpecl (four outputs); two channels are lvds/cmos (up to four lvds outputs or up to eight cmos outputs). each channel has its own programmable divider that divides the clock frequency applied to its input. the lvpecl channel dividers can divide by any integer from 2 to 32, or the divider can be bypassed to achieve a divide by one. each lvds/cmos channel divider contains two of these divider blocks in a cascaded configuration. the total division of the channel is the product of the divide value of the cascaded dividers. this allows divide values of (1 to 32) (1 to 32), or up to 1024 (notice that this is not all values from 1 to 1024 but only the set of numbers that are the product of the two dividers). because the internal vco frequency is above the maximum channel divider input frequency (1600 mhz), the vco divider must be used after the on-chip vco. the vco divider can be set to divide by 2, 3, 4, 5, or 6. external clock signals connected to the clk input also require the vco divider if the frequency of the signal is greater than 1600 mhz. the channel dividers allow for a selection of various duty cycles, depending on the currently set division. that is, for any specific division, d, the output of the divider can be set to high for n + 1 input clock cycles and low for m + 1 input clock cycles (where d = n + m + 2). for example, a divide-by-5 can be high for one divider input cycle and low for four cycles, or a divide- by-5 can be high for three divider input cycles and low for two cycles. other combinations are also possible. the channel dividers include a duty-cycle correction function that can be disabled. in contrast to the selectable duty cycle just described, this function can correct a non-50% duty cycle caused by an odd division. however, this requires that the division be set by m = n + 1. in addition, the channel dividers allow a coarse phase offset or delay to be set. depending on the division selected, the output can be delayed by up to 31 input clock cycles. the divider outputs can also be set to start high or to start low. internal vco or external clk as clock source the clock distribution of the ad9517 has two clock input sources: an internal vco or an external clock connected to the clk/ clk pins. either the internal vco or clk must be chosen as the source of the clock signal to distribute. when the internal vco is selected as the source, the vco divider must be used. when clk is selected as the source, it is not necessary to use the vco divider if the clk frequency is less than the maximum channel divider input frequency (1600 mhz); otherwise, the vco divider must be used to reduce the frequency to one acceptable by the channel dividers. shows how the vco, clk, and vco divider are selected. register 0x1e1[1:0] selects the channel divider source and determines whether the vco divider is used. it is not possible to select the vco without using the vco divider. table 30 table 30. selecting vco or clk as source for channel divider, and whether vco divider is used register 0x1e1 channel divider source vco divider 1 0 0 0 clk used 0 1 clk not used 1 0 vco used 1 1 not allowed not allowed clk or vco direct to lvpecl outputs it is possible to connect either the internal vco or the clk (whichever is selected as the input to the vco divider) directly to the lvpecl outputs, out0 to out3. this configuration can pass frequencies up to the maximum frequency of the vco directly to the lvpecl outputs. the lvpecl outputs may not be able to provide a full voltage swing at the highest frequencies.
ad9517-1 rev. a | page 41 of 80 to connect the lvpecl outputs directly to the internal vco or clk, the vco divider must be selected as the source to the distribution section, even if no channel uses it. either the internal vco or the clk can be selected as the source for the direct-to-output routing. table 31. settings for routing vco divider input directly to lvpecl outputs register setting selection 0x1e1[1:0] = 00b clk is the source; vco divider selected 0x1e1[1:0] = 10b vco is the source; vco divider selected 0x192[1] = 1b direct to output out0, out1 0x198[1] = 1b direct to output out2, out3 clock frequency division the total frequency division is a combination of the vco divider (when used) and the channel divider. when the vco divider is used, the total division from the vco or clk to the output is the product of the vco divider (2, 3, 4, 5, and 6) and the division of the channel divider. table 32 and table 33 indicate how the frequency division for a channel is set. for the lvpecl outputs, there is only one divider per channel. for the lvds/ cmos outputs, there are two dividers (x.1, x.2) cascaded per channel. table 32. frequency division for divider 0 and divider 1 clk or vco selected vco divider channel divider direct to output frequency division clk/vco 2 to 6 1 (bypassed) yes 1 clk/vco 2 to 6 1 (bypassed) no (2 to 6) (1) clk/vco 2 to 6 2 to 32 no (2 to 6) (2 to 32) clk not used 1 (bypassed) no 1 clk not used 2 to 32 no 2 to 32 table 33. frequency division for divider 2 and divider 3 clk or vco selected vco divider channel divider frequency division x.1 x.2 clk/vco 2 to 6 1 (bypassed) 1 (bypassed) (2 to 6) (1) (1) clk/vco 2 to 6 2 to 32 1 (bypassed) (2 to 6) (2 to 32) (1) clk/vco 2 to 6 2 to 32 2 to 32 (2 to 6) (2 to 32) (2to 32) clk not used 1 1 1 clk not used 2 to 32 1 (2 to 32) (1) clk not used 2 to 32 2 to 32 2 to 32 (2 to 32) the channel dividers feeding the lvpecl output drivers contain one 2-to-32 frequency divider. this divider provides for division by 2 to 32. division by 1 is accomplished by bypassing the divider. the dividers also provide for a programmable duty cycle, with optional duty-cycle correction when the divide ratio is odd. a phase offset or delay in increments of the input clock cycle is selectable. the channel dividers operate with a signal at their inputs up to 1600 mhz. the features and settings of the dividers are selected by programming the appropriate setup and control registers (see table 52 through table 62 ). vco divider the vco divider provides frequency division between the internal vco or the external clk input and the clock distribution channel dividers. the vco divider can be set to divide by 2, 3, 4, 5, or 6 (see table 60 , register 0x1e0[2:0]). channel dividerslvpecl outputs each pair of lvpecl outputs is driven by a channel divider. there are two channel dividers (0, 1) driving four lvpecl outputs (out0 to out3). tabl e 34 gives the register locations used for setting the division and other functions of these dividers. the division is set by the values of m and n. the divider can be bypassed (equivalent to divide-by-1, divider circuit is powered down) by setting the bypass bit. the duty-cycle correction can be enabled or disabled according to the setting of the dccoff bits. table 34. setting d x for divider 0 and divider 1 1 divider low cycles m high cycles n bypass dccoff 0 0x190[7:4] 0x190[3:0] 0x191[7] 0x192[0] 1 0x196[7:4] 0x196[3:0] 0x197[7] 0x198[0] 1 note that the value stored in the register = # of cycles minus 1. channel frequency division (0, 1) for each channel (where the channel number is x: 0, 1), the frequency division, d x , is set by the values of m and n (four bits each, representing decimal 0 to decimal 15), where number of low cycles = m + 1 number of high cycles = n + 1 the cycles are cycles of the clock signal currently routed to the input of the channel dividers (vco divider out or clk). when a divider is bypassed, d x = 1. otherwise, d x = (n + 1) + (m + 1) = n + m + 2. this allows each channel divider to divide by any integer from 2 to 32.
ad9517-1 rev. a | page 42 of 80 d uty cycle and duty-cycle correction (0, 1) t he duty cycle of the clock signal at the output of a channel is a result of some or all of the following conditions: ? what are the m and n values for the channel? ? is the dcc enabled? ? is the vco divider used? ? what is the clk input duty cycle? (the internal vco has a 50% duty cycle.) t he dcc function is enabled by default for each channel divider. however, the dcc function can be disabled individually for each channel divider by setting the dccoff bit for that channel. c ertain m and n values for a channel divider result in a non-50% duty cycle. a non-50% duty cycle can also result with an even division, if m n. the duty-cycle correction function automatically corrects non-50% duty cycles at the channel divider output to 50% duty cycle. duty-cycle correction requires the following channel divider conditions: ? an even division must be set as m = n. ? an odd division must be set as m = n + 1. when not bypassed or corrected by the dcc function, the duty cycle of each channel divider output is the numerical value of (n + 1)/(n + m + 2), expressed as %. the duty cycle at the output of the channel divider for various configurations is shown in table 35 to table 37 . table 35. duty cycle with vco divider; input duty cycle is 50% vco divider d x output duty cycle n + m + 2 dccoff = 1 dccoff = 0 even 1 (divider bypassed) 50% 50% odd = 3 1 (divider bypassed) 33.3% 50% odd = 5 1 (divider bypassed) 40% 50% even, odd even (n + 1)/ (n + m + 2) 50%; requires m = n even, odd odd (n + 1)/ (n + m + 2) 50%; requires m = n + 1 table 36. duty cycle with vco divider; input duty cycle is x% vco divider d x output duty cycle n + m + 2 dccoff = 1 dccoff = 0 even 1 (divider bypassed) 50% 50% odd = 3 1 (divider bypassed) 33.3% (1 + x%)/3 odd = 5 1 (divider bypassed) 40% (2 + x%)/5 even even (n + 1)/ (n + m + 2) 50%, requires m = n odd (n + 1)/ (n + m + 2) 50%, requires m = n + 1 odd = 3 even (n + 1)/ (n + m + 2) 50%, requires m = n odd = 3 odd (n + 1)/ (n + m + 2) (3n + 4 + x%)/(6n + 9), requires m = n + 1 odd = 5 even (n + 1)/ (n + m + 2) 50%, requires m = n odd = 5 odd (n + 1)/ (n + m + 2) (5n + 7 + x%)/(10n + 15), requires m = n + 1 table 37. channel divider output duty cycle when the vco divider is not used input clock duty cycle d x output duty cycle n + m + 2 dccoff = 1 dccoff = 0 any 1 1 (divider bypassed) same as input duty cycle any even (n + 1)/ (m + n + 2) 50%, requires m = n 50% odd (n + 1)/ (m + n + 2) 50%, requires m = n + 1 x% odd (n + 1)/ (m + n + 2) (n + 1 + x%)/(2 n + 3), requires m = n + 1 the internal vco has a duty cycle of 50%. therefore, when the vco is connected directly to the output, the duty cycle is 50%. if the clk input is routed directly to the output, the duty cycle of the output is the same as the clk input.
ad9517-1 rev. a | page 43 of 80 phase offset or coarse time delay (0, 1) each channel divider allows for a phase offset, or a coarse time delay, to be programmed by setting register bits (see table 38 ). these settings determine the number of cycles (successive rising edges) of the channel divider input frequency by which to offset, or delay, the rising edge of the output of the divider. this delay is with respect to a nondelayed output (that is, with a phase offset of zero). the amount of the delay is set by five bits loaded into the phase offset (po) register plus the start high (sh) bit for each channel divider. when the start high bit is set, the delay is also affected by the number of low cycles (m) programmed for the divider. the sync function must be used to make phase offsets effective (see the synchronizing the outputssync function section). table 38. setting phase offset and division for divider 0 and divider 1 divider start high (sh) phase offset (po) low cycles m high cycles n 0 0x191[4] 0x191[3:0] 0x190[7:4] 0x190[3:0] 1 0x197[4] 0x197[3:0] 0x196[7:4] 0x196[3:0] let t = delay (in seconds). c = delay (in cycles of clock signal at input to d x ). t x = period of the clock signal at the input of the divider, d x (in seconds). = 16 sh[4] + 8 po[3] + 4 po[2] + 2 po[1] + 1 po[0] the channel divide-by is set as n = high cycles and m = low cycles. case 1 for 15: t = t x c = t/t x = case 2 for 16: t = ( ? 16 + m + 1) t x c = t/t x by giving each divider a different phase offset, output-to-output delays can be set in increments of the channel divider input clock cycle. figure 54 shows the results of setting such a coarse offset between outputs. c h a n n e l d i v i d e r o u t p u t s d i v = 4 , d u t y = 5 0 % 0123456789101112131415 tx divider 0 divider 1 divider 2 channel divider input sh = 0 po = 0 sh = 0 po = 1 sh = 0 po = 2 1 tx 2 tx 06425-071 figure 54. effect of coarse phase offset (or delay) channel dividerslvds/cmos outputs channel divider 2 and channel divider 3 each drive a pair of lvds outputs, giving four lvds outputs (out4 to out7). alternatively, each of these lvds differential outputs can be configured individually as a pair (a and b) of cmos single- ended outputs, providing for up to eight cmos outputs. by default, the b output of each pair is off but can be turned on as desired. channel divider 2 and channel divider 3 each consist of two cascaded, 2 to 32, frequency dividers. the channel frequency division is d x.1 d x.2 or up to 1024. divide-by-1 is achieved by bypassing one or both of these dividers. both of the dividers also have dcc enabled by default, but this function can be disabled, if desired, by setting the dccoff bit of the channel. a coarse phase offset or delay is also programmable (see the phase offset or coarse time delay (divider 2 and divider 3) section). the channel dividers operate up to 1600 mhz. the features and settings of the dividers are selected by programming the appropriate setup and control registers (see table 52 and table 53 through table 62 ). table 39. setting division (d x ) for divider 2, divider 3 1 divider m n bypass dccoff 2 2.1 0x199[7:4] 0x199[3:0] 0x19c[4] 0x19d[0] 2.2 0x19b[7:4] 0x19b[3:0] 0x19c[5] 0x19d[0] 3 3.1 0x19e[7:4] 0x19e[3:0] 0x1a1[4] 0x1a2[0] 3.2 0x1a0[7:4] 0x1a0[3: 0] 0x1a1[5] 0x1a2[0] 1 note that the value stored in the register = # of cycles minus 1. channel frequency division (divider 2 and divider 3) the division for each channel divider is set by the bits in the registers for the individual dividers (x.y = 2.1, 2.2, 3.1, and 3.2) number of low cycles = m x.y + 1 number of high cycles = n x.y + 1 when both x.1 and x.2 are bypassed, d x = 1 1 = 1. when only x.2 is bypassed, d x = (n x.1 + m x.1 + 2) 1. when both x.1 and x.2 are not bypassed, d x = (n x.1 + m x.1 + 2) (n x.2 + m x.2 + 2). by cascading the dividers, channel division up to 1024 can be obtained. however, not all integer value divisions from 1 to 1024 are obtainable; only the values that are the product of the separate divisions of the two dividers (d x.1 d x.2 ) can be realized. if only one divider is needed when using divider 2 and divider 3, use the first one (x.1) and bypass the second one (x.2). do not bypass x.1 and use x.2.
ad9517-1 rev. a | page 44 of 80 duty cycle and duty-cycle correction (divider 2 and divider 3) the same duty cycle and dcc considerations apply to divider 2 and divider 3 as to divider 0 and divider 1 (see the duty cycle and duty-cycle correction (0, 1) section); however, with these channel dividers, the number of possible configurations is even more complex. duty-cycle correction on divider 2 and divider 3 requires the following channel divider conditions: ? an even d x.y must be set as m x.y = n x.y (low cycles = high cycles). ? an odd d x.y must be set as m x.y = n x.y + 1 (the number of low cycles must be one greater than the number of high cycles). ? if only one divider is bypassed, it must be the second divider, x.2. ? if only one divider has an even divide-by, it must be the second divider, x.2. the possibilities for the duty cycle of the output clock from divider 2 and divider 3 are shown in table 40 through table 44. table 40. divider 2 and divide r 3 duty cycle; vco divider used; duty cycle correction off (dccoff = 1) vco divider d x.1 d x.2 output duty cycle n x.1 + m x.1 + 2 n x.2 + m x.2 + 2 even 1 1 50% odd = 3 1 1 33.3% odd = 5 1 1 40% even even, odd 1 (n x.1 + 1)/ (n x.1 + m x.1 + 2) odd even, odd 1 (n x.1 + 1)/ (n x.1 + m x.1 + 2) even even, odd even, odd (n x.2 + 1)/ (n x.2 + m x.2 + 2) odd even, odd even, odd (n x.2 + 1)/ (n x.2 + m x.2 + 2) table 41. divider 2 and divide r 3 duty cycle; vco divider not used; duty cycle correction off (dccoff = 1) input clock duty cycle d x.1 d x.2 output duty cycle n x.1 + m x.1 + 2 n x.2 + m x.2 + 2 50% 1 1 50% x% 1 1 x% 50% even, odd 1 (n x.1 + 1)/ (n x.1 + m x.1 + 2) x% even, odd 1 (n x.1 + 1)/ (n x.1 + m x.1 + 2) 50% even, odd even, odd (n x.2 + 1)/ (n x.2 + m x.2 + 2) x% even, odd even, odd (n x.2 + 1)/ (n x.2 + m x.2 + 2) table 42. divider 2 and divide r 3 duty cycle; vco divider used; duty cycle correction is on (dccoff = 0); vco divider input duty cycle = 50% vco divider d x.1 d x.2 output duty cycle n x.1 + m x.1 + 2 n x.2 + m x.2 + 2 even 1 1 50% odd 1 1 50% even even (n x.1 = m x.1 ) 1 50% odd even (n x.1 = m x.1 ) 1 50% even odd (m x.1 = n x.1 + 1) 1 50% odd odd (m x.1 = n x.1 + 1) 1 50% even even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% odd even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% even odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% odd odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% even odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) 50% odd odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) 50% table 43. divider 2 and divide r 3 duty cycle; vco divider used; duty cycle correction on (dccoff = 0); vco divider input duty cycle = x% vco divider d x.1 d x.2 output duty cycle n x.1 + m x.1 + 2 n x.2 + m x.2 + 2 even 1 1 50% odd = 3 1 1 (1 + x%)/3 odd = 5 1 1 (2 + x%)/5 even even (n x.1 = m x.1 ) 1 50% odd even (n x.1 = m x.1 ) 1 50% even odd (m x.1 = n x.1 + 1) 1 50% odd = 3 odd (m x.1 = n x.1 + 1) 1 (3n x.1 + 4 + x%)/ (6n x.1 + 9) odd = 5 odd (m x.1 = n x.1 + 1) 1 (5n x.1 + 7 + x%)/ (10n x.1 + 15) even even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% odd even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% even odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% odd odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% even odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) 50% odd = 3 odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) (6n x.1 n x.2 + 9n x.1 + 9n x.2 + 13 + x%)/ (3(2n x.1 + 3) (2n x.2 + 3)) odd = 5 odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) (10n x.1 n x.2 + 15n x.1 + 15n x.2 + 22 + x%)/ (5(2 n x.1 + 3) (2 n x.2 + 3))
ad9517-1 rev. a | page 45 of 80 table 44. divider 2 and divide r 3 duty cycle; vco divider not used; duty cycle correction on (dccoff = 0) input clock duty cycle d x.1 d x.2 output duty cycle n x.1 + m x.1 + 2 n x.2 + m x.2 + 2 50% 1 1 50% 50% even (n x.1 = m x.1 ) 1 50% x% 1 1 x% (high) x% even (n x.1 = m x.1 ) 1 50% 50% odd (m x.1 = n x.1 + 1) 1 50% x% odd (m x.1 = n x.1 + 1) 1 (n x.1 + 1 + x%)/ (2n x.1 + 3) 50% even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% x% even (n x.1 = m x.1 ) even (n x.2 = m x.2 ) 50% 50% odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% x% odd (m x.1 = n x.1 + 1) even (n x.2 = m x.2 ) 50% 50% odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) 50% x% odd (m x.1 = n x.1 + 1) odd (m x.2 = n x.2 + 1) (2n x.1 n x.2 + 3n x.1 + 3n x.2 + 4 + x%)/ ((2n x.1 + 3)(2n x.2 + 3)) phase offset or coarse time delay (divider 2 and divider 3) divider 2 and divider 3 can be set to have a phase offset or delay. the phase offset is set by a combination of the bits in the phase offset and start high registers (see table 4 5 ). table 45. setting phase offset and division for divider 2 and divider 3 divider start high (sh) phase offset (po) low cycles m high cycles n 2 2.1 0x19c[0] 0x19a[3:0] 0x199[7:4] 0x199[3:0] 2.2 0x19c[1] 0x19a[7:4] 0x19b[7:4] 0x19b[3:0] 3 3.1 0x1a1[0] 0x19f[3:0] 0x19e[7:4] 0x19e[3:0] 3.2 0x1a1[1] 0x19f[7:4] 0x1a0[7:4] 0x1a0[3:0] let t = delay (in seconds). x.y = 16 sh[0] + 8 po[3] + 4 po[2] + 2 po[1] + 1 po[0]. t x.1 = period of the clock signal at the input to d x.1 (in seconds). t x.2 = period of the clock signal at the input to d x.2 (in seconds). case 1 when x.1 15 and x.2 15: t = x.1 t x.1 + x.2 t x.2 case 2 when x.1 15 and x.2 16: t = x.1 t x.1 + ( x.2 ? 16 + m x.2 + 1) t x.2 case 3 when x.1 16 and x.2 15: t = ( x.1 ? 16 + m x.1 + 1) t x.1 + x.2 t x.2 case 4 when x.1 16 and x.2 16: t = ( x.1 ? 16 + m x.1 + 1) t x.1 + ( x.2 ? 16 + m x.2 + 1) t x.2 fine delay adjust (divider 2 and divider 3) each ad9517 lvds/cmos output (out4 to out7) includes an analog delay element that can be programmed to give variable time delays (t) in the clock signal at that output. divider x.2 divider x.1 t outm outm bypass fine delay adjust cmos lvds cmos t outn outn bypass fine delay adjust cmos lvds cmos output drivers clk vco divider 06425-072 figure 55. fine delay (out4 to out7) the amount of delay applied to the clock signal is determined by programming four registers per output (see table 46 ). table 46. setting analog fine delays output (lvds/cmos) ramp capacitors ramp current delay fraction delay bypass out4 0x0a1[5:3] 0x0a1[2:0] 0x0a2[5:0] 0x0a0[0] out5 0x0a4[5:3] 0x0a4[2:0] 0x0a5[5:0] 0x0a3[0] out6 0x0a7[5:3] 0x0a7[2:0] 0x0a8[5:0] 0x0a6[0] out7 0x0aa[5:3] 0x0aa[2:0] 0x0ab[5:0] 0x0a9[0]
ad9517-1 rev. a | page 46 of 80 calculating the fine delay the following values and equations are used to calculate the delay of the delay block. i ramp (a) = 200 ( ramp current + 1) number of capacitors = number of bits = 0 in ramp capacitor s + 1 example: 101 = 1 + 1 = 2; 110 = 1 + 1 = 2; 100 = 2 + 1 = 3; 001 = 2 + 1 = 3; 111 = 0 + 1 = 1. delay range (ns) = 200 (( no. of caps + 3)/( i ramp )) 1.3286 () () 6 1 10 16000.34ns 4 ? ? ? ? ? ? ? ?? +?+= ? ramp ramp i capsofno. i offset delay full scale (ns) = delay range + offset fine delay (ns) = delay range delay fraction (1/63) + offset note that only delay fraction values up to 47 decimal (101111b; 0x2f) are supported. in no case can the fine delay exceed one-half of the output clock period. if a delay longer than half of the clock period is attempted, the output stops clocking. the delay function adds some jitter greater than that specified for the nondelayed output. this means that the delay function should be used primarily for clocking digital chips, such as fpga, asic, duc, and ddc. an output with this delay enabled may not be suitable for clocking data converters. the jitter is higher for long full scales because the delay block uses a ramp and trip points to create the variable delay. a slower ramp time produces more time jitter. synchronizing the outputssync function the ad9517 clock outputs can be synchronized to each other. outputs can be individually excluded from synchronization. synchronization consists of setting the nonexcluded outputs to a preset set of static conditions and subsequently releasing these outputs to continue clocking at the same instant with the preset conditions applied. this allows for the alignment of the edges of two or more outputs or for the spacing of edges according to the coarse phase offset settings for two or more outputs. s ynchronization of the outputs is executed in several ways: ? the sync pin is forced low and then released (manual sync). ? by setting and then resetting any one of the following three bits: the soft sync bit (register 0x230[0]), the soft reset bit (register 0x000[2] [mirrored]), and the distribution power- down bit (register 0x230[1]). ? synchronization of the outputs can be executed as part of the chip power-up sequence. ? the reset pin is forced low and then released (chip reset). ? the pd pin is forced low, then released (chip power-down). ? when a vco calibration is completed, an internal sync signal is automatically asserted at the beginning and released upon the completion of a vco calibration. the most common way to execute the sync function is to use the sync pin to do a manual synchronization of the outputs. this requires a low-going signal on the sync pin, which is held low and then released when synchronization is desired. the timing of the sync operation is shown in (using vco divider) and (vco divider not used). there is an uncertainty of up to one cycle of the clock at the input to the channel divider due to the asynchronous nature of the sync signal with respect to the clock edges inside the ad9517. the delay from the figure 56 figure 57 sync rising edge to the beginning of synchronized output clocking is between 14 and 15 cycles of clock at the channel divider input, plus either one cycle of the vco divider input (see ), or one cycle of the channel divider input (see ), depending on whether the vco divider is used. cycles are counted from the rising edge of the signal. figure 56 figure 57 another common way to execute the sync function is by setting and resetting the soft sync bit at register 0x230[0] (see table 53 through table 6 2 for details). both setting and resetting of the soft sync bit require an update all registers (register 0x232[0] = 1) operation to take effect.
ad9517-1 rev. a | page 47 of 80 1234567 8 910 input to vco divider input to channel divider output of channel divider s ync pin 1 11 12 13 14 14 to 15 cycles at channel divider input + 1 cycle at vco divider input channel divider output static channel divide r output clocking channel divide r output clocking 06425-073 figure 56. sync timing when vco divider is usedclk or vco is input input to clk iinput to channel divider output of channel divider sync pin 14 to 15 cycles at channel divider input + 1 cycle at clk input 1234567 8 910 11 12 13 14 1 channel divider output static channel divide r output clocking channel divider output clocking 0 6425-074 figure 57. sync timing when vco di vider is not usedclk input only a sync operation brings all outputs that have not been excluded (by the nosync bit) to a preset condition before allowing the outputs to begin clocking in synchronicity. the preset condition takes into account the settings in each of the channels start high bit and its phase offset. these settings govern both the static state of each output when the sync operation is happening and the state and relative phase of the outputs when they begin clocking again upon completion of the sync operation. between outputs and after synchronization, this allows for the setting of phase offsets. the ad9517 outputs are in pairs, sharing a channel divider per pair (two pairs of pairs, four outputs, in the case of cmos). the synchronization conditions apply to both outputs of a pair. each channel (a divider and its outputs) can be excluded from any sync operation by setting the nosync bit of the channel. channels that are set to ignore sync (excluded channels) do not set their outputs static during a sync operation, and their outputs are not synchronized with those of the nonexcluded channels. clock outputs the ad9517 offers three output level choices: lvpecl, lvds, and cmos. out0 to out3 are lvpecl differential outputs; and out4 to out7 are lvds/cmos outputs. these outputs can be configured as either lvds differential or as pairs of single-ended cmos outputs.
ad9517-1 rev. a | page 48 of 80 lvpecl outputsout0 to out3 the lvpecl differential voltage (v od ) is selectable from ~400 mv to ~960 mv (see register 0x0f0[3:2] to register 0x0f5[3:2]). the lvpecl outputs have dedicated pins for power supply (vs_lvpecl), allowing a separate power supply to be used. v s_lvpecl can be from 2.5 v to 3.3 v. the lvpecl output polarity can be set as noninverting or inverting, which allows for the adjustment of the relative polarity of outputs within an application without requiring a board layout change. each lvpecl output can be powered down or powered up as needed. because of the architecture of the lvpecl output stages, there is the possibility of electrical overstress and breakdown under certain power-down conditions. for this reason, the lvpecl outputs have several power-down modes. this includes a safe power-down mode that continues to protect the output devices while powered down, although it consumes somewhat more power than a total power-down. if the lvpecl output pins are terminated, it is best to select the safe power-down mode. if the pins are not connected (unused), it is acceptable to use the total power-down mode. gnd 3.3 v out out 06425-033 figure 58. lvpecl output simplified equivalent circuit lvds/cmos outputsout4 to out7 out4 to out7 can be configured as either an lvds differential output or as a pair of cmos single-ended outputs. the lvds outputs allow for selectable output current from ~1.75 ma to ~7 ma. the lvds output polarity can be set as noninverting or inverting, which allows for the adjustment of the relative polarity of outputs within an application without requiring a board layout change. each lvds output can be powered down if not needed to save power. out4 to out7 can also be cmos outputs. each lvds output can be configured to be two cmos outputs. this provides for up to eight cmos outputs: out4a, out4b, out5a, out5b, out6a, out6b, out7a, and out7b. when an output is configured as cmos, cmos output a is automatically turned on. cmos output b can be turned on or off independently. the relative polarity of the cmos outputs can also be selected for any combination of inverting and noninverting (see table 57 , register 0x140[7:5], register 0x141[7:5], register 0x142[7:5], and register 0x143[7:5]). out out 3 .5m a 3 .5m a 06425-034 figure 59. lvds output simplified equivalent circuit with 3.5 ma typical current source each lvds/cmos output can be powered-down as needed to save power. the cmos output power-down is controlled by the same bit that controls the lvds power-down for that output. this power-down control affects both the cmos a and cmos b outputs. however, when the cmos a output is powered up, the cmos b output can be powered on or off separately. out v s 06425-035 figure 60. cmos equivalent output circuit reset modes the ad9517 has several ways to force the chip into a reset condition that restores all registers to their default values and makes these settings active. power-on resetstart-up conditions when v s is applied a power-on reset (por) is issued when the v s power supply is turned on. this initializes the chip to the power-on conditions that are determined by the default register settings. these are indicated in the default value (hex) column of table 52 . at power-on, the ad9517 also executes a sync operation, which brings the outputs into phase alignment according to the default settings. asynchronous reset via the reset pin an asynchronous hard reset is executed by momentarily pulling reset low. a reset restores the chip registers to the default settings. soft reset via register 0x00[2] a soft reset is executed by writing register 0x000[2] and register 0x000[5] = 1b. this bit is not self-clearing; it must be cleared by writing register 0x000[2] and register 0x000[5] = 0b to reset it and complete the soft reset operation. a soft reset restores the default values to the internal registers. the soft reset bit does not require an update registers command (register 0x232) to be issued.
ad9517-1 rev. a | page 49 of 80 power-down modes chip power-down via pd the ad9517 can be put into a power-down condition by pulling the pd pin low. power-down turns off most of the functions and currents inside the ad9517. the chip remains in this power-down state until pd is brought back to logic high. when the ad9517 wakes it, it returns to the settings programmed into its registers prior to the power-down, unless the registers are changed by new programming while the pd pin is held low. the pd power-down shuts down the currents on the chip, except the bias current necessary to maintain the lvpecl outputs in a safe shutdown mode. this is needed to protect the lvpecl output circuitry from damage that could be caused by certain termination and load configurations when tristated. because this is not a complete power-down, it can be called sleep mode. w hen the ad9517 is in a pd power-down, the chip is in the following state: ? the pll is off (asynchronous power-down). ? the vco is off. ? the clk input buffer is off. ? all dividers are off. ? all lvds/cmos outputs are off. ? all lvpecl outputs are in safe off mode. ? the serial control port is active, and the chip responds to commands. if the ad9517 clock outputs must be synchronized to each other, a sync is required upon exiting power-down (see the synchronizing the outputssync function section). a vco calibration is not required when exiting power-down. pll power-down the pll section of the ad9517 can be selectively powered down. there are three pll operating modes set by register 0x010[1:0], as shown in table 54 . in asynchronous power-down mode, the device powers down as soon as the registers are updated. in synchronous power-down mode, the pll power-down is gated by the charge pump to prevent unwanted frequency jumps. the device goes into power-down on the occurrence of the next charge pump event after the registers are updated. distribution power-down the distribution section can be powered down by writing register 0x230[1] = 1b. this turns off the bias to the distribution section. if the lvpecl power-down mode is normal operation (00b), it is possible for a low impedance load on that lvpecl output to draw significant current during this power-down. if the lvpecl power-down mode is set to 11b, the lvpecl output is not protected from reverse bias and may be damaged under certain termination conditions. individual clock output power-down any of the clock distribution outputs can be powered down individually by writing to the appropriate registers. the register map details the individual power-down settings for each output (see table 52 ). the lvds/cmos outputs can be powered down, regardless of their output load configuration. the lvpecl outputs have multiple power-down modes (see table 56 ), which give some flexibility in dealing with the various output termination conditions. when the mode is set to 10b, the lvpecl output is protected from reverse bias to 2 vbe + 1 v. if the mode is set to 11b, the lvpecl output is not protected from reverse bias and can be damaged under certain termination conditions. this setting also affects the operation when the distribution block is powered down with register 0x230[1] = 1b (see the distribution power-down section). individual circuit block power-down other ad9517 circuit blocks (such as clk, ref1, and ref2) can be powered down individually. this gives flexibility in configuring the part for power savings whenever certain chip functions are not needed.
ad9517-1 rev. a | page 50 of 80 serial control port the ad9517 serial control port is a flexible, synchronous, serial communications port that allows an easy interface with many industry-standard microcontrollers and microprocessors. the ad9517 serial control port is compatible with most synchronous transfer formats, including both the motorola spi? and intel? ssr? protocols. the serial control port allows read/write access to all registers that configure the ad9517. single or multiple byte transfers are supported, as well as msb first or lsb first transfer formats. the ad9517 serial control port can be configured for a single bidirectional i/o pin (sdio only) or for two unidirectional i/o pins (sdio/sdo). by default, the ad9517 is in bidirectional mode, long instruction (long instruction is the only instruction mode supported). serial control port pin descriptions sclk (serial clock) is the serial shift clock. this pin is an input. sclk is used to synchronize serial control port reads and writes. write data bits are registered on the rising edge of this clock, and read data bits are registered on the falling edge. this pin is internally pulled down by a 30 k resistor to ground. sdio (serial data input/output) is a dual-purpose pin and acts as either an input only (unidirectional mode) or as both an input/output (bidirectional mode). the ad9517 defaults to the bidirectional i/o mode (register 0x000[0] = 0). sdo (serial data out) is used only in the unidirectional i/o mode (register 0x000[0] = 1) as a separate output pin for reading back data. cs (chip select bar) is an active low control that gates the read and write cycles. when cs is high, sdo and sdio are in a high impedance state. this pin is internally pulled up by a 30 k resistor to vs. ad9517-1 serial control port sclk 13 cs 14 sdo 15 sdio 16 06425-036 figure 61. serial control port general operation of serial control port a write or a read operation to the ad9517 is initiated by pulling cs low. cs stalled high is supported in modes where three or fewer bytes of data (plus instruction data) are transferred (see ). in these modes, table 47 cs can temporarily return high on any byte boundary, allowing time for the system controller to process the next byte. cs can go high on byte boundaries only and can go high during either part (instruction or data) of the transfer. during this period, the serial control port state machine enters a wait state until all data is sent. if the system controller decides to abort the transfer before all of the data is sent, the state machine must be reset by either completing the remaining transfers or by returning the cs low for at least one complete sclk cycle (but less than eight sclk cycles). raising the cs on a nonbyte boundary terminates the serial transfer and flushes the buffer. in the streaming mode (see table 47 ), any number of data bytes can be transferred in a continuous stream. the register address is automatically incremented or decremented (see the msb/lsb first transfers section). cs must be raised at the end of the last byte to be transferred, thereby ending the stream mode. communication cycleinstruction plus data there are two parts to a communication cycle with the ad9517. the first part writes a 16-bit instruction word into the ad9517, coincident with the first 16 sclk rising edges. the instruction word provides the ad9517 serial control port with information regarding the data transfer, which is the second part of the communication cycle. the instruction word defines whether the upcoming data transfer is a read or a write, the number of bytes in the data transfer, and the starting register address for the first byte of the data transfer. write if the instruction word is for a write operation, the second part is the transfer of data into the serial control port buffer of the ad9517. data bits are registered on the rising edge of sclk. the length of the transfer (1, 2, 3 bytes or streaming mode) is indicated by two bits (w1:w0) in the instruction byte. when the transfer is 1, 2, or 3 bytes, but not streaming, cs can be raised after each sequence of eight bits to stall the bus (except after the last byte, where it ends the cycle). when the bus is stalled, the serial transfer resumes when cs is lowered. raising cs on a nonbyte boundary resets the serial control port. during a write, streaming mode does not skip over reserved or blank registers, and it does not matter what data is written to blank registers. because data is written into a serial control port buffer area, not directly into the actual control registers of the ad9517, an additional operation is needed to transfer the serial control port buffer contents to the actual control registers of the ad9517, thereby causing them to become active. the update registers operation consists of setting regi ster 0x232[0] = 1b (this bit is self-clearing). any number of bytes of data can be changed before executing an update registers. the update registers simultaneously actuates all register changes that have been written to the buffer since any previous update.
ad9517-1 rev. a | page 51 of 80 read if the instruction word is for a read operation, the next n 8 sclk cycles clock out the data from the address specified in the instruction word, where n is 1 to 3 as determined by [w1:w0]. if n = 4, the read operation is in streaming mode, continuing until cs is raised. streaming mode does not skip over reserved or blank registers. the readback data is valid on the falling edge of sclk. the default mode of the ad9517 serial control port is the bidirectional mode. in bidirectional mode, both the sent data and the readback data appear on the sdio pin. it is also possible to set the ad9517 to unidirectional mode via the sdo active bit, register 0x000[0] = 1. in unidirectional mode, the readback data appears on the sdo pin. a readback request reads the data that is in the serial control port buffer area, or the data that is in the active registers (see figure 62 ). readback of the buffer or active registers is controlled by register 0x004[0]. the ad9517 supports only the long instruction mode; therefore, register 0x000[4:3] must be set to 11b. long instruction mode is the default at power-up or reset. the ad9517 uses register address 0x000 to register address 0x232. sclk sdio sdo cs serial control port buffer registers update registers write register 0x232 = 0x01 to udate registers active registers 06425-037 figure 62. relationship between seri al control port buffer registers and active registers of the ad9517 the instruction word (16 bits) the msb of the instruction word is r/ w , which indicates whether the instruction is a read or a write. the next two bits, [w1:w0], indicate the length of the transfer in bytes. the final 13 bits are the address ([a12:a0]) at which to begin the read or write operation. for a write, the instruction word is followed by the number of bytes of data indicated by bits[w1:w0] (see table 47 ). table 47. byte transfer count w1 w0 bytes to transfer 0 0 1 0 1 2 1 0 3 1 1 streaming mode the 13 bits found in [a12:a0] select the address within the register map that is written to or read from during the data transfer portion of the communications cycle. only bits[a9:a0] are needed to cover the range of the 0x232 registers used by the ad9517. bits[a12:a10] must always be 0b. for multibyte transfers, this address is the starting byte address. in msb first mode, subsequent bytes increment the address. msb/lsb first transfers the ad9517 instruction word and byte data can be msb first or lsb first. any data written to register 0x000 must be mirrored; the upper four bits (bits[7:4]) must mirror the lower four bits (bits[3:0). this makes it irrelevant whether lsb first or msb first is in effect. as an example of this mirroring, see the default setting for this register: 0x18, which mirrors bit 4 and bit 3. this sets the long instruction mode (which is the default and is the only mode supported). the default for the ad9517 is msb first. when lsb first is set by register 0x000[1] and register 0x000[6], it takes effect immediately because it affects only the operation of the serial control port and does not require that an update be executed. when msb first mode is active, the instruction and data bytes must be written from msb to lsb. multibyte data transfers in msb first format start with an instruction byte that includes the register address of the most significant data byte. subsequent data bytes must follow in order from the high address to the low address. in msb first mode, the serial control port internal address generator decrements for each data byte of the multibyte transfer cycle. when lsb first is active, the instruction and data bytes must be written from lsb to msb. multibyte data transfers in lsb first format start with an instruction byte that includes the register address of the least significant data byte followed by multiple data bytes. the internal byte address generator of the serial control port increments for each byte of the multibyte transfer cycle. the ad9517 serial control port register address decrements from the register address just written toward 0x000 for multibyte i/o operations if the msb first mode is active (default). if the lsb first mode is active, the register address of the serial control port increments from the address just written toward 0x232 for multibyte i/o operations. streaming mode always terminates when it hits address 0x232. note that unused addresses are not skipped during multibyte i/o operations. table 48. streaming mode (no addresses are skipped) write mode address direction stop sequence lsb first increment 0x230, 0x231, 0x232, stop msb first decrement 0x001, 0x000, 0x232, stop
ad9517-1 rev. a | page 52 of 80 table 49. serial control port, 16-bit instruction word, msb first msb lsb i15 i14 i13 i12 i11 i10 i9 i8 i7 i6 i5 i4 i3 i2 i1 i0 r/ w w1 w0 a12 = 0 a11 = 0 a10 = 0 a9 a8 a7 a6 a5 a4 a3 a2 a1 a0 cs scl k don't care sdio a12 w0 w1 r/w a11 a10 a9 a8 a7 a6 a5 a4 a3 a2 a1 a0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 don't care don't care don't care 16-bit instruction header register (n) data register (n ? 1) data 0 6425-038 figure 63. serial control port writemsb fi rst, 16-bit instruct ion, two bytes data cs sclk sdio sdo register (n) data 16-bit instruction header register (n ? 1) data register (n ? 2) data register (n ? 3) data a12 w0 w1 r/w a11 a10 a9 a8 a7 a6 a5 a4 a3 a2 a1 a0 don?t care don?t care don?t care don?t care d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 d7 d6 d5 d4 d3 d2 d1 d0 06425-039 figure 64. serial control port readmsb fi rst, 16-bit instruction, four bytes data t s don?t care don?t care w1w0a12a11a10a9a8a7a6a5d4d3d2d1d0 don?t care don?t care r/w t ds t dh t high t low t clk t c cs sclk sdio 06425-040 figure 65. serial control port writemsb firs t, 16-bit instruction, timing measurements data bit n ? 1 data bit n cs sclk sdio sdo t dv 06425-041 figure 66. timing diagram for serial control port register read cs sclk don't care don't care 16-bit instruction header register (n) data register (n + 1) data sdio don't care don't care a0 a1 a2 a3 a4 a5 a6 a7 a8 a9 a10 a11 a12 d1d0r/w w1 w0 d2 d3 d4 d5 d6 d7 d0 d1 d2 d3 d4 d5 d6 d7 0 6425-042 figure 67. serial control port writelsb fi rst, 16-bit instruction, two bytes data
ad9517-1 rev. a | page 53 of 80 cs sclk sdio t high t low t clk t s t ds t dh t c bit n bit n + 1 06425-043 figure 68. serial control port timingwrite table 50. serial control port timing parameter description t ds setup time between data and rising edge of sclk t dh hold time between data and rising edge of sclk t clk period of the clock setup time between cs falling edge and sclk rising edge (start of communication cycle) t s setup time between sclk rising edge and cs rising edge (end of communication cycle) t c t high minimum period that sclk should be in a logic high state t low minimum period that sclk should be in a logic low state t dv sclk to valid sdio and sdo (see figure 66 )
ad9517-1 rev. a | page 54 of 80 thermal performance table 51. thermal parameters for the 48-lead lfcsp symbol thermal characteristic using a jedec jesd51-7 plus jedec jesd51-5 2s2p test board value (c/w) ja junction-to-ambient thermal resistance, natural convection per jedec jesd51-2 (still air) 24.7 jma junction-to-ambient thermal resistance, 1.0 m/sec airflow per jedec jesd51-6 (moving air) 21.6 jma junction-to-ambient thermal resistance, 2.5 m/sec airflow per jedec jesd51-6 (moving air) 19.4 jb junction-to-board thermal resistance, natural convection per jedec jesd51-8 (still air) 12.9 jb junction-to-board characterization parameter, na tural convection per jedec jesd51-6 (still air) and jedec jesd51-8 11.9 jb junction-to-board characterization parameter, 1.0 m/sec airflow per jedec jesd51-6 (moving air) and jedec jesd51-8 11.8 jb junction-to-board characterization parameter, 2.5 m/sec airflow per jedec jesd51-6 (moving air) and jedec jesd51-8 11.6 jc junction-to-case thermal resistance (die-to-heat sink) per mil-std-883, method 1012.1 1.3 jt junction-to-top-of-package characterization parameter, natural convection per jedec jesd51-2 (still air) 0.1 jt junction-to-top-of-package characterization paramete r, 1.0 m/sec airflow per jedec jesd51-2 (still air) 0.2 jt junction-to-top-of-package characterization paramete r, 2.0 m/sec airflow per jedec jesd51-2 (still air) 0.3 the ad9517 is specified for a case temperature (t case ). to ensure that t case is not exceeded, an airflow source can be used. use the following equation to determine the junction temperature on the application pcb: t j = t case + ( jt pd ) where: t j is the junction temperature (c). t case is the case temperature (c) measured by the user at the top center of the package. jt is the value from table 51 . pd is the power dissipation (see the total power dissipation in table 17 ). va lu e s of ja are provided for package comparison and pcb design considerations. ja can be used for a first-order approximation of t j by the equation t j = t a + ( ja pd ) where t a is the ambient temperature (c). va lu e s of jc are provided for package comparison and pcb design considerations when an external heat sink is required. va lu e s of jb are provided for package comparison and pcb design considerations.
ad9517-1 rev. a | page 55 of 80 control registers control register map overview table 52. control register map overview reg. addr (hex) parameter bit 7 (msb) bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 (lsb) default value (hex) serial port configuration 0x000 serial port configuration sdo active lsb first soft reset long instruction long instruction soft reset lsb first sdo active 0x18 0x001 blank 0x002 reserved 0x003 part id part id (read only) 0x51 0x004 read back control blank read back active registers 0x00 pll 0x010 pfd and charge pump pfd polarity charge pump current charge pu mp mode pll power-down 0x7d 0x011 r counter 14-bit r divi der, bits[7:0] (lsb) 0x01 0x012 blank 14-bit r divide r, bits[13:8] (msb) 0x00 0x013 a counter blank 6-bit a counter 0x00 0x014 b counter 13-bit b counter, bits[7:0] (lsb) 0x03 0x015 blank 13-bit b counter, bits[12:8] (msb) 0x00 0x016 pll control 1 set cp pin to v cp /2 reset r counter reset a and b counters reset all counters b counter bypass prescaler p 0x06 0x017 pll control 2 status pin control antibacklash pulse width 0x00 0x018 pll control 3 reserved lock detect counter digital lock detect window disable digital lock detect vco calibration divider vco cal now 0x06 0x019 pll control 4 r, a, b counters sync pin reset r path delay n path delay 0x00 0x01a pll control 5 reserved reference frequency monitor threshold ld pin control 0x00 0x01b pll control 6 vco frequency monitor ref2 ( refin ) frequency monitor ref1 (refin) frequency monitor refmon pin control 0x00 0x01c pll control 7 disable switchover deglitch select ref2 use ref_sel pin automatic reference switchover stay on ref2 ref2 power-on ref1 power-on differential reference 0x00 0x01d pll control 8 reserved pll status register disable ld pin comparator enable holdover enable external holdover control holdover enable 0x00 0x01e pll control 9 reserved 0x00 0x01f pll readback reserved vco cal finished holdover active ref2 selected vco frequency > threshold ref2 frequency > threshold ref1 frequency > threshold digital lock detect n/a 0x020 to 0x04f blank
ad9517-1 rev. a | page 56 of 80 reg. addr (hex) parameter bit 7 (msb) bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 (lsb) default value (hex) fine delay adjustout4 to out7 0x0a0 out4 delay bypass blank out4 delay bypass 0x01 0x0a1 out4 delay full-scale blank out4 ramp capacitors out4 ramp current 0x00 0x0a2 out4 delay fraction blank out4 delay fraction 0x00 0x0a3 out5 delay bypass blank out5 delay bypass 0x01 0x0a4 out5 delay full-scale blank out5 ramp capacitors out5 ramp current 0x00 0x0a5 out5 delay fraction blank out5 delay fraction 0x00 0x0a6 out6 delay bypass blank out6 delay bypass 0x01 0x0a7 out6 delay full-scale blank out6 ramp capacitors out6 ramp current 0x00 0x0a8 out6 delay fraction blank out6 delay fraction 0x00 0x0a9 out7 delay bypass blank out7 delay bypass 0x01 0x0aa out7 delay full-scale blank out7 ramp capacitors out7 ramp current 0x00 0x0ab out7 delay fraction blank out7 delay fraction 0x00 0x0ac to 0x0ef blank lvpecl outputs 0x0f0 out0 blank out0 invert out0 lvpecl differential voltage out0 power-down 0x08 0x0f1 out1 blank out1 invert out1 lvpecl differential voltage out1 power-down 0x0a 0x0f2, 0x0f3 reserved 0x0f4 out2 blank out2 invert out2 lvpecl differential voltage out2 power-down 0x08 0x0f5 out3 blank out3 invert out3 lvpecl differential voltage out3 power-down 0x0a 0x0f6 to 0x13f blank lvds/cmos outputs 0x140 out4 out4 cmos output polarity out4 lvds/ cmos output polarity out4 cmos b out4 select lvds/cmos out4 lvds output current out4 power-down 0x42 0x141 out5 out5 cmos output polarity out5 lvds/ cmos output polarity out5 cmos b out5 select lvds/cmos out5 lvds output current out5 power-down 0x43 0x142 out6 out6 cmos output polarity out6 lvds/ cmos output polarity out6 cmos b out6 select lvds/cmos out6 lvds output current out6 power-down 0x42 0x143 out7 out7 cmos output polarity out7 lvds/ cmos output polarity out7 cmos b out7 select lvds/cmos out7 lvds output current out7 power-down 0x43 0x144 to 0x18f blank
ad9517-1 rev. a | page 57 of 80 reg. addr (hex) parameter bit 7 (msb) bit 6 bit 5 bit 4 bit 3 bit 2 bit 1 bit 0 (lsb) default value (hex) lvpecl channel dividers 0x190 divider 0 (pecl) divider 0 low cycles divi der 0 high cycles 0x00 0x191 divider 0 bypass divider 0 nosync divider 0 force high divider 0 start high divider 0 phase offset 0x80 0x192 blank reserved divider 0 direct to output divider 0 dccoff 0x00 0x193 to 0x195 reserved 0x196 divider1 (pecl) divider 1 low cycles divi der 1 high cycles 0x00 0x197 divider 1 bypass divider 1 nosync divider 1 force high divider 1 start high divider 1 phase offset 0x00 0x198 blank reserved divider 1 direct to output divider 1 dccoff 0x00 lvds/cmos channel dividers 0x199 divider 2 (lvds/cmos) low cycles divider 2.1 high cycles divider 2.1 0x22 0x19a phase offset divider 2.2 phase offset divider 2.1 0x00 0x19b low cycles divider 2.2 high cycles divider 2.2 0x11 0x19c reserved bypass divider 2.2 bypass divider 2.1 divider 2 nosync divider 2 force high start high divider 2.2 start high divider 2.1 0x00 0x19d blank reserved divider 2 dccoff 0x00 0x19e divider 3 (lvds/cmos) low cycles divider 3.1 high cycles divider 3.1 0x22 0x19f phase offset divider 3.2 phase offset divider 3.1 0x00 0x1a0 low cycles divider 3.2 high cycles divider 3.2 0x11 0x1a1 reserved bypass divider 3.2 bypass divider 3.1 divider 3 nosync divider 3 force high start high divider 3.2 start high divider 3.1 0x00 0x1a2 blank reserved divider 3 dccoff 0x00 0x1a3 reserved 0x1a4 to 0x1df blank vco divider and clk input 0x1e0 vco divider blank reserved vco divider 0x02 0x1e1 input clks reserved power- down clock input section power-down vco clock interface power- down vco and clk select vco or clk bypass vco divider 0x00 0x1e2 to 0x22a blank system 0x230 power-down and sync reserved power- down sync power- down distribution reference soft sync 0x00 0x231 blank reserved 0x00 update all registers 0x232 update all registers blank update all registers (self- clearing bit) 0x00
ad9517-1 rev. a | page 58 of 80 control register map descriptions table 53 through table 62 provide a detailed description of each of the control register functions. the registers are listed by hexadecimal address. a range of bits (for example, from bit 5 through bit 2) is indicated using a colon and brackets, like this: [5:2]. table 53. serial port configuration and part id reg. addr (hex) bits name description 0x000 [7:4] mirrored, bits[3:0] bits[7:4] should always mirror bits[3:0] so th at it does not matter whether the part is in msb or lsb first mode (see bit 1, regist er 0x000). user should set bits as follows: bit 7 = bit 0. bit 6 = bit 1. bit 5 = bit 2. bit 4 = bit 3. 3 long instruction short/long instruction mode. this part uses lo ng instruction mode only, so this bit should always be 1. 0: 8-bit instruction (short). 1: 16-bit instruction (long) (default). 2 soft reset soft reset. 1: soft reset; restores default values to internal registers. not self-clearing. must be cleared to 0 to complete reset operation. 1 lsb first msb or lsb data orientation. 0: data-oriented msb first; addressing decrements (default). 1: data-oriented lsb first; addressing increments. 0 sdo active selects unidirectional or bidirectional data transfer mode. 0: sdio pin used for write and read; sdo set high impedance; bidirectional mode (default). 1: sdo used for read, sdio used for write; unidirectional mode. 0x003 [7:0] part id (read only) uniquely identifies the dash version (-0 through -4) of the ad9517 ad9517-0: 0x11 ad9517-1: 0x51 ad9517-2: 0x91 ad9517-3: 0x53 ad9517-4: 0xd3 0x004 0 read back active registers select register bank used for a readback. 0: read back buffer registers (default). 1: read back active registers.
ad9517-1 rev. a | page 59 of 80 table 54. pll reg. addr. (hex) bits name description 0x010 7 pfd polarity sets the pfd polarity. negative polarity is for use (if needed) with external vco/vcxo only. the on-chip v co requires positive polarity; bit 7 = 0. 0: positive; higher control voltag e produces higher frequency (default). 1: negative; higher control voltage produces lower frequency. [6:4] cp current charge pump current (with cprset = 5.1 k). 6 5 4 i cp (ma) 0 0 0 0.6 0 0 1 1.2 0 1 0 1.8 0 1 1 2.4 1 0 0 3.0 1 0 1 3.6 1 1 0 4.2 1 1 1 4.8 (default) [3:2] cp mode charge pump operating mode. 3 2 charge pump mode 0 0 high impedance state. 0 1 force source current (pump up). 1 0 force sink current (pump down). 1 1 normal operation (default). [1:0] pll power- pll operating mode. down 1 0 mode 0 0 normal operation. 0 1 asynchronous power-down (default). 1 0 normal operation. 1 1 synchronous power-down. 0x011 [7:0] 14-bit r divider, bits[7:0] (lsb) r divider lsbslower eight bits (default = 0x01). 0x012 [5:0] 14-bit r divider, bits[13:8] (msb) r divider msbsupper six bits (default = 0x00). 0x013 [5:0] 6-bit a counter a counter (part of n divider) (default = 0x00). 0x014 [7:0] 13-bit b counter, bits[7:0] (lsb) b counter (part of n divider)lower eight bits (default = 0x03). 0x015 [4:0] 13-bit b counter, bits[12:8] (msb) b counter (part of n divider)upper five bits (default = 0x00). 0x016 7 set cp pin to v cp /2 set the cp pin to one-half of the v cp supply voltage. 0: cp normal operation (default). 1: cp pin set to v cp /2. 6 reset r counter reset r counter (r divider). 0: normal (default). 1: holds the r counter in reset. 5 reset a, b counters reset a and b counters (part of n divider). 0: normal (default). 1: holds the a and b counters in reset. 4 reset all counters reset r, a, and b counters. 0: normal (default). 1: holds the r, a, and b counters in reset. 3 b counter b counter bypass. this is valid on ly when operating the prescaler in fd mode. bypass 0: normal (default). 1: b counter is set to divide-by-1. this allows the prescaler setting to determine the divide for the n divider.
ad9517-1 rev. a | page 60 of 80 reg. addr. (hex) bits name description 0x016 [2:0] prescaler p prescaler: dm = dual modulus and fd = fixed divide. 2 1 0 mode prescaler 0 0 0 fd divide-by-1. 0 0 1 fd divide-by-2. 0 1 0 dm divide-by-2 (2/3 mode). 0 1 1 dm divide-by-4 (4/5 mode). 1 0 0 dm divide-by-8 (8/9 mode). 1 0 1 dm divide-by-16 (16/17 mode). 1 1 0 dm divide-by-32 (32/33 mode) (default). 1 1 1 fd divide-by-3. 0x017 [7:2] status pin select the signal that is connected to the status pin. control 7 6 5 4 3 2 level or dynamic signal signal at status pin 0 0 0 0 0 0 lvl ground (dc) (default). 0 0 0 0 0 1 dyn n divider output (after the delay). 0 0 0 0 1 0 dyn r divider output (after the delay). 0 0 0 0 1 1 dyn a divider output. 0 0 0 1 0 0 dyn prescaler output. 0 0 0 1 0 1 dyn pfd up pulse. 0 0 0 1 1 0 dyn pfd down pulse. 0 x x x x x lvl ground (dc); for all other cases of 0xxxxx not specified above. the selections that follow are the same as refmon. 1 0 0 0 0 0 lvl ground (dc). 1 0 0 0 0 1 dyn ref1 clock (differential reference when in differential mode). 1 0 0 0 1 0 dyn ref2 clock (n/a in differential mode). 1 0 0 0 1 1 dyn selected reference to pll (differential reference when in differential mode). 1 0 0 1 0 0 dyn unselected reference to pll (not available in differential mode). 1 0 0 1 0 1 lvl status of selected refere nce (status of differential reference); active high. 1 0 0 1 1 0 lvl status of unselected re ference (not available in differential mode); active high. 1 0 0 1 1 1 lvl status ref1 frequency (active high). 1 0 1 0 0 0 lvl status ref2 frequency (active high). 1 0 1 0 0 1 lvl (status ref1 frequency) and (status ref2 frequency). 1 0 1 0 1 0 lvl (dld) and (status of selected reference) and (status of vco). 1 0 1 0 1 1 lvl status of vco frequency (active high). 1 0 1 1 0 0 lvl selected reference (low = ref1, high = ref2). 1 0 1 1 0 1 lvl digital lock detect (dld); active high. 1 0 1 1 1 0 lvl holdover active (active high). 1 0 1 1 1 1 lvl ld pin comparator output (active high). 1 1 0 0 0 0 lvl vs (pll supply). 1 1 0 0 0 1 dyn ref1 clock (differential reference when in differential mode). 1 1 0 0 1 0 dyn ref2 clock (not available in differential mode). 1 1 0 0 1 1 dyn selected reference to pll (differential reference when in differential mode). 1 1 0 1 0 0 dyn unselected reference to pll (not available when in differential mode). 1 1 0 1 0 1 lvl status of selected referenc e (status of differential reference); active low. 1 1 0 1 1 0 lvl status of unselected reference (not available in differential mode); active low. 1 1 0 1 1 1 lvl status of ref1 frequency (active low). 1 1 1 0 0 0 lvl status of ref2 frequency (active low). 1 1 1 0 0 1 lvl (status of ref1 frequency) and (status of ref2 frequency) . 1 1 1 0 1 0 lvl (dld) and (status of selected reference) and (status of vco) . 1 1 1 0 1 1 lvl status of vco frequency (active low). 1 1 1 1 0 0 lvl selected reference (low = ref2, high = ref1). 1 1 1 1 0 1 lvl digital lock detect (dld) (active low). 1 1 1 1 1 0 lvl holdover active (active low). 1 1 1 1 1 1 lvl ld pin comparator output (active low).
ad9517-1 rev. a | page 61 of 80 reg. addr. (hex) bits name description 0x017 [1:0] antibacklash 1 0 antibacklash pulse width (ns) pulse width 0 0 2.9 (default). 0 1 1.3. 1 0 6.0. 1 1 2.9. 0x018 [6:5] lock detect counter required consecutive number of pfd cycles with edges insi de lock detect window before the dld indicates a locked condition. 6 5 pfd cycles to determine lock 0 0 5 (default). 0 1 16. 1 0 64. 1 1 255. 4 digital lock detect window if the time difference of the rising edges at the inputs to the pfd are less than the lock detect window time, the digital lock detect flag is set. the flag remains set until the time difference is greater than the loss-of-lock threshold. 0: high range (default). 1: low range. 3 disable digital digital lock detect operation. lock detect 0: normal lock detect operation (default). 1: disable lock detect. [2:1] vco cal vco calibration divider. divider used to gene rate the vco calibration clock from the pll reference clock. divider 2 1 vco calibration clock divider 0 0 2. 0 1 4. 1 0 8. 1 1 16 (default). [0] vco cal now bit used to initiate the vco calibration. this bi t must be toggled from 0 to 1 in the active registers. to ini tiate calibration, use the following three steps: first, ensure that the input reference signal is present; second, set to 0 (if not zero already), followed by an update bi t (register 0x232, bit 0); and third, pr ogram to 1, followed by another update bit (register 0x232, bit 0). 0x019 [7:6] r, a, b counters 7 6 action sync pin reset 0 0 do nothing on sync (default). 0 1 asynchronous reset. 1 0 synchronous reset. 1 1 do nothing on sync . [5:3] r path delay r path delay (see table 2 ) (default = 0x00). [2:0] n path delay n path delay (see table 2 ) (default = 0x00). 0x01a [6] reference frequency monitor sets the reference (ref1/ref2) frequency monitors detect ion threshold frequency. this does not affect the vco frequency monitors detection threshold (see table 16 , ref1, ref2, and vco frequency status monitor). threshold 0: frequency valid if frequency is above the higher frequency threshold (default). 1: frequency valid if frequency is above the lower frequency threshold.
ad9517-1 rev. a | page 62 of 80 reg. addr. (hex) bits name description 0x01a [5:0] ld pin control select the sign al that is connected to the ld pin. 5 4 3 2 1 0 level or dynamic signal signal at ld pin 0 0 0 0 0 0 lvl digital lock detect (high = lock, low = unlock) (default). 0 0 0 0 0 1 dyn p-channel, open-dra in lock detect (analog lock detect). 0 0 0 0 1 0 dyn n-channel, open-dra in lock detect (analog lock detect). 0 0 0 0 1 1 hiz high-z ld pin. 0 0 0 1 0 0 cur current source lock detect (110 a when dld is true). 0 x x x x x lvl ground (dc); for all other cases of 0xxxxx not specified above. the selections that follow are the same as refmon. 1 0 0 0 0 0 lvl ground (dc). 1 0 0 0 0 1 dyn ref1 clock (different ial reference when in differential mode). 1 0 0 0 1 0 dyn ref2 clock (n/a in differential mode). 1 0 0 0 1 1 dyn selected reference to pll (differential reference when indifferential mode). 1 0 0 1 0 0 dyn unselected reference to pll (not available in differential mode). 1 0 0 1 0 1 lvl status of selected reference (status of differential reference); active high. 1 0 0 1 1 0 lvl status of unselected re ference (not available in differential mode); active high. 1 0 0 1 1 1 lvl status ref1 frequency (active high). 1 0 1 0 0 0 lvl status ref2 frequency (active high). 1 0 1 0 0 1 lvl (status ref1 frequency) and (status ref2 frequency). 1 0 1 0 1 0 lvl (dld) and (status of selected reference) and (status of vco). 1 0 1 0 1 1 lvl status of vco frequency (active high). 1 0 1 1 0 0 lvl selected reference (low = ref1, high = ref2). 1 0 1 1 0 1 lvl digital lock detect (dld); active high. 1 0 1 1 1 0 lvl holdover active (active high). 1 0 1 1 1 1 lvl n/a. do not use. 1 1 0 0 0 0 lvl vs (pll supply). 1 1 0 0 0 1 dyn ref1 clock (differential reference when in differential mode). 1 1 0 0 1 0 dyn ref2 clock (not available in differential mode). 1 1 0 0 1 1 dyn selected reference to pll (differential reference when in differential mode). 1 1 0 1 0 0 dyn unselected reference to pll (not available when in differential mode). 1 1 0 1 0 1 lvl status of selected reference (status of differential reference); active low. 1 1 0 1 1 0 lvl status of unselected re ference (not available in differential mode); active low. 1 1 0 1 1 1 lvl status of ref1 frequency (active low). 1 1 1 0 0 0 lvl status of ref2 frequency (active low). 1 1 1 0 0 1 lvl (status of ref1 frequency) an d (status of ref2 frequency) . 1 1 1 0 1 0 lvl (dld) and (status of selected reference) and (status of vco) . 1 1 1 0 1 1 lvl status of vco frequency (active low). 1 1 1 1 0 0 lvl selected reference (low = ref2, high = ref1). 1 1 1 1 0 1 lvl digital lock detect (dld); active low. 1 1 1 1 1 0 lvl holdover active (active low). 1 1 1 1 1 1 lvl n/ado not use. 0x01b 7 vco enable or disable vco frequency monitor. frequency monitor 0: disable vco frequency monitor (default). 1: enable vco frequency monitor. 6 ref2 ( refin ) enable or disable ref2 frequency monitor. frequency monitor 0: disable ref2 frequency monitor (default). 1: enable ref2 frequency monitor. 5 ref1 (refin) frequency monitor ref1 (refin) frequency monitor enable; this is for both ref1 (single-ended) and refin (differential) inputs (as selected by differential reference mode). 0: disable ref1 (refin) frequency monitor (default). 1: enable ref1 (refin) frequency monitor.
ad9517-1 rev. a | page 63 of 80 reg. addr. (hex) bits name description 0x01b [4:0] refmon select the signal that is connected to the refmon pin. pin control 4 3 2 1 0 level or dynamic signal signal at refmon pin 0 0 0 0 0 lvl ground (dc) (default). 0 0 0 0 1 dyn ref1 clock (differentia l reference when in differential mode). 0 0 0 1 0 dyn ref2 clock (n/a in differential mode). 0 0 0 1 1 dyn selected reference to pll (differential reference when in differential mode). 0 0 1 0 0 dyn unselected reference to pll (not available in differential mode). 0 0 1 0 1 lvl status of selected reference (status of differential reference); active high. 0 0 1 1 0 lvl status of unselected reference (not available in differential mode); active high. 0 0 1 1 1 lvl status ref1 frequency (active high). 0 1 0 0 0 lvl status ref2 frequency (active high). 0 1 0 0 1 lvl (status ref1 freq uency) and (status ref2 frequency). 0 1 0 1 0 lvl (dld) and (status of se lected reference) and (status of vco). 0 1 0 1 1 lvl status of vco frequency (active high). 0 1 1 0 0 lvl selected reference (low = ref1, high = ref2). 0 1 1 0 1 lvl digital lock detect (dld); active low. 0 1 1 1 0 lvl holdover active (active high). 0 1 1 1 1 lvl ld pin comparator output (active high). 1 0 0 0 0 lvl vs (pll supply). 1 0 0 0 1 dyn ref1 clock (differential reference when in differential mode). 1 0 0 1 0 dyn ref2 clock (not available in differential mode). 1 0 0 1 1 dyn selected reference to pll (differential reference when in differential mode). 1 0 1 0 0 dyn unselected reference to pll (not available when in differential mode). 1 0 1 0 1 lvl status of selected reference (status of differential reference); active low. 1 0 1 1 0 lvl status of unse lected reference (not available in differential mode); active low. 1 0 1 1 1 lvl status of ref1 frequency (active low). 1 1 0 0 0 lvl status of ref2 frequency (active low). 1 1 0 0 1 lvl (status of ref1 frequency) an d (status of ref2 frequency) . 1 1 0 1 0 lvl (dld) and (status of selected reference) and (status of vco) . 1 1 0 1 1 lvl status of vco frequency (active low). 1 1 1 0 0 lvl selected reference (low = ref2, high = ref1). 1 1 1 0 1 lvl digital lock detect (dld); active low. 1 1 1 1 0 lvl holdover active (active low). 1 1 1 1 1 lvl ld pin comparator output (active low). 0x01c 7 disable disable or enable the switchover deglitch circuit. switchover 0: enable switchover deglitch circuit (default). deglitch 1: disable switchover deglitch circuit. 6 select ref2 if register 0x01c, bit 5 = 0, select reference for pll. 0: select ref1 (default). 1: select ref2. 5 use ref_sel pin if register 0x01c, bit 4 = 0 (manual), set method of pl l reference selection. 0: use register 0x01c[6]. (default) 1: use ref_sel pin. 4 automatic automatic or manual reference switchover. single-ended reference mode must be selected by register 0x01c, bit 0 = 0. reference 0: manual reference switchover (default). switchover 1: automatic reference switchover. 3 stay on ref2 stay on ref2 after switchover. 0: return to ref1 automatically when ref1 status is good again (default). 1: stay on ref2 after switchover. do not automatically return to ref1. 2 ref2 power-on when automatic reference switchov er is disabled, this bit turns the ref2 power on. 0: ref2 power off (default). 1: ref2 power on.
ad9517-1 rev. a | page 64 of 80 reg. addr. (hex) bits name description 0x01c 1 ref1 power-on when automatic reference switch over is disabled, this bit turns the ref1 power on. 0: ref1 power off (default). 1: ref1 power on. 0 differential reference selects the pll reference mode, differential or single-end ed. single-ended must be selected for the automatic switchover or ref1 and ref2 to work. 0: single-ended reference mode (default). 1: differential reference mode. 0x01d 4 pll status disables the pll status register readback. register disable 0: pll status register enable (default). 1: pll status register disable. 3 ld pin comparator enable enables the ld pin voltage comparator. this is used with the ld pin current source lock detect mode. when in the internal (automatic) holdover mode, this enables the use of the voltage on the ld pin to determine if the pll was previously in a locked state (see figure 52 ). otherwise, this can be used with the refmon and status pins to monitor the voltage on this pin. 0: disable ld pin comparator; internal/automatic holdov er controller treats this pi n as true (high) (default). 1: enable ld pin comparator. 2 holdover enable along with bit 0, enables the holdover functi on. automatic holdover must be disabled during vco calibration. 0: holdover disabled (default). 1: holdover enabled. 1 external enables the external hold control through the sync pin. (this disables the internal holdover mode.) holdover control 0: automatic holdover modeholdove r controlled by automatic ho ldover circuit. (default) 1: external holdover m odeholdover controlled by sync pin. 0 holdover enable along with bit 2, enables the holdover functi on. automatic holdover must be disabled during vco calibration. 0: holdover disabled (default). 1: holdover enabled. 0x01f 6 vco cal finished read-only register: status of the vco calibration. 0: vco calibration not finished. 1: vco calibration finished. 5 holdover active read-only register: indicates if the part is in the holdover state (see figure 52 ). this is not the same as holdover enabled. 0: not in holdover. 1: holdover state active. 4 ref2 selected read-only register: indicates which p ll reference is selected as the input to the pll. 0: ref1 selected (or differential reference if in differential mode). 1: ref2 selected. 3 vco frequency > threshold read-only register: indicates if the vco frequency is greater than the threshold (see table 16 , ref1, ref2, and vco frequency status monitor). 0: vco frequency is less than the threshold. 1: vco frequency is greater than the threshold. 2 ref2 frequency > threshold read-only register: indicates if the frequency of the signal at ref2 is greater than the threshold frequency set by register 0x1a, bit 6. 0: ref2 frequency is less than threshold frequency. 1: ref2 frequency is grea ter than threshold frequency. 1 ref1 frequency > threshold read-only register: indicates if the frequency of the sign al at ref2 is greater than the threshold frequency set by register 0x01a, bit 6. 0: ref1 frequency is less than threshold frequency. 1: ref1 frequency is grea ter than threshold frequency. 0 digital lock detect read-only register: digital lock detect. 0: pll is not locked. 1: pll is locked.
ad9517-1 rev. a | page 65 of 80 table 55. fine delay adjustout4 to out7 reg. addr. (hex) bits name description 0x0a0 0 out4 delay bypass bypass or use the delay function. 0: use delay function. 1: bypass delay function (default). 0x0a1 [5:3] out4 ramp capacitors selects the number of ramp capacitors used by the delay function. the combination of the number of the capacitors and the ramp current sets the delay full scale. 5 4 3 number of capacitors 0 0 0 4 (default) 0 0 1 3 0 1 0 3 0 1 1 2 1 0 0 3 1 0 1 2 1 1 0 2 1 1 1 1 [2:0] out4 ramp current ramp current for the delay function. the combinat ion of the number of capacitors and the ramp current sets the delay full scale. 2 1 0 current (a) 0 0 0 200 (default) 0 0 1 400 0 1 0 600 0 1 1 800 1 0 0 1000 1 0 1 1200 1 1 0 1400 1 1 1 1600 0x0a2 [5:0] out4 delay fraction selects the fraction of the full-scale delay desired (6-bit binary). 000000 gives zero delay. only delay values up to 47 decimals (101 111b; 0x2f) are supported (default = 0x00). 0x0a3 0 out5 delay bypass bypass or use the delay function. 0: use delay function. 1: bypass delay function (default). 0x0a4 [5:3] out5 ramp capacitors selects the number of ramp capacitors used by the delay function. the combination of the number of the capacitors and the ramp current sets the delay full scale. 5 4 3 number of capacitors 0 0 0 4 (default) 0 0 1 3 0 1 0 3 0 1 1 2 1 0 0 3 1 0 1 2 1 1 0 2 1 1 1 1
ad9517-1 rev. a | page 66 of 80 reg. addr. (hex) bits name description 0x0a4 [2:0] out5 ramp current ramp current for the delay function. the combinat ion of the number of capacitors and the ramp current sets the delay full scale. 2 1 0 current (a) 0 0 0 200 (default) 0 0 1 400 0 1 0 600 0 1 1 800 1 0 0 1000 1 0 1 1200 1 1 0 1400 1 1 1 1600 0x0a5 [5:0] out5 delay fraction selects the fraction of the full-scale delay desired (6-bit binary). 000000 give zero delay. only delay values up to 47 decimals (101111b; 0x2f) are supported (default = 0x00). 0x0a6 0 out6 delay bypass bypass or use the delay function. 0: use delay function. 1: bypass delay function (default). 0x0a7 [5:3] out6 ramp capacitors selects the number of ramp capacitors used by the delay function. the combination of the number of capacitors and the ramp current sets the delay full scale. 5 4 3 number of capacitors 0 0 0 4 (default) 0 0 1 3 0 1 0 3 0 1 1 2 1 0 0 3 1 0 1 2 1 1 0 2 1 1 1 1 [2:0] out6 ramp current ramp current for the delay function. the combinatio n of the number of capacitors and the ramp current sets the delay full scale. 2 1 0 current (a) 0 0 0 200 (default) 0 0 1 400 0 1 0 600 0 1 1 800 1 0 0 1000 1 0 1 1200 1 1 0 1400 1 1 1 1600 0x0a8 [5:0] out6 delay fraction selects the fraction of the full-scale delay desired (6-bit binary). 000000 gives zero delay. only delay values up to 47 decimals (101111b; 0x2f) are supported (default = 0x00). 0x0a9 0 out7 delay bypass bypass or use the delay function. 0: use delay function. 1: bypass delay function (default).
ad9517-1 rev. a | page 67 of 80 reg. addr. (hex) bits name description 0x0aa [5:3] out7 ramp capacitors selects the number of ramp capacitors used by the delay function. the combination of the number of capacitors and the ramp current sets the delay full scale. 5 4 3 number of capacitors 0 0 0 4 (default) 0 0 1 3 0 1 0 3 0 1 1 2 1 0 0 3 1 0 1 2 1 1 0 2 1 1 1 1 [2:0] out7 ramp current ramp current for the delay function. the combinat ion of the number of capacitors and the ramp current sets the delay full scale. 2 1 0 current value (a) 0 0 0 200 (default) 0 0 1 400 0 1 0 600 0 1 1 800 1 0 0 1000 1 0 1 1200 1 1 0 1400 1 1 1 1600 0x0ab [5:0] out7 delay fraction selects the fraction of the full-scale delay desired (6-bit binary). 000000 gives zero delay. only delay values up to 47 decimals (101111b; 0x2f) are supported (default = 0x00). table 56. lvpecl outputs reg. addr. (hex) bits name description 0x0f0 4 out0 invert sets the output polarity. 0: noninverting (default). 1: inverting. [3:2] out0 lvpecl sets the lvpecl output differential voltage (v od ). differential voltage 3 2 v od (mv) 0 0 400 0 1 600 1 0 780 (default) 1 1 960 [1:0] out0 power-down lvpecl power-down modes. 1 0 mode output 0 0 normal operation (default). on 0 1 partial power-down, reference on; use only if there are no external load resistors. off 1 0 partial power-down, reference on, safe lvpecl power-down. off 1 1 total power-down, reference off; use only if there are no external load resistors. off
ad9517-1 rev. a | page 68 of 80 reg. addr. (hex) bits name description 0x0f1 4 out1 invert sets the output polarity. 0: noninverting (default). 1: inverting. [3:2] out1 lvpecl sets the lvpecl output differential voltage (v od ). differential voltage 3 2 v od (mv) 0 0 400 0 1 600 1 0 780 (default) 1 1 960 [1:0] out1 power-down lvpecl power-down modes. 1 0 mode output 0 0 normal operation. on 0 1 partial power-down, reference on; use only if there are no external load resistors. off 1 0 partial power-down, reference on, safe lvpecl power-down (default). off 1 1 total power-down, reference off; use only if there are no external load resistors. off 0x0f4 4 out2 invert sets the output polarity. 0: noninverting (default). 1: inverting. [3:2] out2 lvpecl sets the lvpecl output differential voltage (v od ). differential voltage 3 2 v od (mv) 0 0 400 0 1 600 1 0 780 (default) 1 1 960 [1:0] out2 power-down lvpecl power-down modes. 1 0 mode output 0 0 normal operation (default). on 0 1 partial power-down, reference on; use only if there are no external load resistors. off 1 0 partial power-down, reference on, safe lvpecl power-down. off 1 1 total power-down, reference off; use only if there are no external load resistors. off 0x0f5 4 out3 invert sets the output polarity. 0: noninverting (default). 1: inverting. [3:2] out3 lvpecl sets the lvpecl output differential voltage (v od ). differential voltage 3 2 v od (mv) 0 0 400 0 1 600 1 0 780 (default) 1 1 960 [1:0] out3 power-down lvpecl power-down modes. 1 0 mode output 0 0 normal operation. on 0 1 partial power-down, reference on; use only if there are no external load resistors. off 1 0 partial power-down, reference on, safe lvpecl power-down (default). off 1 1 total power-down, reference off; use only if there are no external load resistors. off
ad9517-1 rev. a | page 69 of 80 table 57. lvds/cmos outputs reg. addr. (hex) bits name description 0x140 [7:5] out4 output polarity in cmos mode, bits[7:5] select the output polarity of each cmos output. in lvds mode, only bit 5 determines lvds polarity. 7 6 5 out4a (cmos) out4b (cmos) out4 (lvds) 0 0 0 noninverting inverting noninverting 0 1 0 noninverting noninverting noninverting (default) 1 0 0 inverting inverting noninverting 1 1 0 inverting noninverting noninverting 0 0 1 inverting noninverting inverting 0 1 1 inverting inverting inverting 1 0 1 noninverting noninverting inverting 1 1 1 noninverting inverting inverting 4 out4 cmos b in cmos mode, turn on/off the cmos b output. there is no effect in lvds mode. 0: turn off the cmos b output (default). 1: turn on the cmos b output. 3 out4 select lvds/cmos select lvds or cmos logic levels. 0: lvds (default). 1: cmos. [2:1] out4 lvds output current set output current leve l in lvds mode. this has no effect in cmos mode. 2 1 current (ma) recommended termination () 0 0 1.75 100 0 1 3.5 100 (default) 1 0 5.25 50 1 1 7 50 0 out4 power-down power-down output (lvds/cmos). 0: power on (default). 1: power off. 0x141 [7:5] out5 output polarity in cmos mode, bits[7:5] select the output polarity of each cmos output. in lvds mode, only bit 5 determines lvds polarity. 7 6 5 out5a (cmos) out5b (cmos) out5 (lvds) 0 0 0 noninverting inverting noninverting 0 1 0 noninverting noninverting noninverting (default) 1 0 0 inverting inverting noninverting 1 1 0 inverting noninverting noninverting 0 0 1 inverting noninverting inverting 0 1 1 inverting inverting inverting 1 0 1 noninverting noninverting inverting 1 1 1 noninverting inverting inverting 4 out5 cmos b in cmos mode, turn on/off the cmos b output. there is no effect in lvds mode. 0: turn off the cmos b output (default). 1: turn on the cmos b output. 3 out5 select lvds/cmos select lvds or cmos logic levels. 0: lvds (default). 1: cmos. [2:1] out5 lvds output current set output current leve l in lvds mode. this has no effect in cmos mode. 2 1 current (ma) recommended termination () 0 0 1.75 100 0 1 3.5 100 (default) 1 0 5.25 50 1 1 7 50
ad9517-1 rev. a | page 70 of 80 reg. addr. (hex) bits name description 0x141 0 out5 power-down power-down output (lvds/cmos). 0: power on. 1: power off (default). 0x142 [7:5] out6 output polarity in cmos mode, bits[7:5] select the output polarity of each cmos output. in lvds mode, only bit 5 determines lvds polarity. 7 6 5 out6a (cmos) out6b (cmos) out6 (lvds) 0 0 0 noninverting inverting noninverting 0 1 0 noninverting noninverting noninverting (default) 1 0 0 inverting inverting noninverting 1 1 0 inverting noninverting noninverting 0 0 1 inverting noninverting inverting 0 1 1 inverting inverting inverting 1 0 1 noninverting noninverting inverting 1 1 1 noninverting inverting inverting 4 out6 cmos b in cmos mode, turn on/off the cmos b output. there is no effect in lvds mode. 0: turn off the cmos b output (default). 1: turn on the cmos b output. 3 out6 select lvds/cmos select lvds or cmos logic levels. 0: lvds (default). 1: cmos. [2:1] out6 lvds output current set output current leve l in lvds mode. this has no effect in cmos mode. 2 1 current (ma) recommended termination () 0 0 1.75 100 0 1 3.5 100 (default) 1 0 5.25 50 1 1 7 50 0 out6 power-down power-down output (lvds/cmos). 0: power on (default). 1: power off. 0x143 [7:5] out7 output polarity in cmos mode, bits[7:5] select the output polarity of each cmos output. in lvds mode, only bit 5 determines lvds polarity. 7 6 5 out7a (cmos) out7b (cmos) out7 (lvds) 0 0 0 noninverting inverting noninverting 0 1 0 noninverting noninverting noninverting (default) 1 0 0 inverting inverting noninverting 1 1 0 inverting noninverting noninverting 0 0 1 inverting noninverting inverting 0 1 1 inverting inverting inverting 1 0 1 noninverting noninverting inverting 1 1 1 noninverting inverting inverting 4 out7 cmos b in cmos mode, turn on/off the cmos b output. there is no effect in lvds mode. 0: turn off the cmos b output (default). 1: turn on the cmos b output. 3 out7 select lvds/cmos select lvds or cmos logic levels. 0: lvds (default). 1: cmos.
ad9517-1 rev. a | page 71 of 80 reg. addr. (hex) bits name description 0x143 [2:1] out7 lvds output current set output current le vel in lvds mode. this has no effect in cmos mode. 2 1 current (ma) recommended termination () 0 0 1.75 100 0 1 3.5 100 (default) 1 0 5.25 50 1 1 7 50 0 out7 power-down power-down output (lvds/cmos). 0: power on. 1: power off (default). table 58. lvpecl channel dividers reg. addr. (hex) bits name description 0x190 [7:4] divider 0 low cycles number of clock cycles (minus 1) of the divider input during which divider output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] divider 0 high cycles number of clock cycles (minus 1) of the di vider input during which divider output stays high. a value of 0x0 means that the divider is high for one input clock cycle (default = 0x0). 0x191 7 divider 0 bypass bypass and power-down th e divider; route input to divider output. 0: use divider. 1: bypass divider (default). 6 divider 0 nosync nosync. 0: obey chip-level sync signal (default). 1: ignore chip-level sync signal. 5 divider 0 force high force divider output to high. this requires that nosync (bit 6) also be set. 0: divider output forced to low (default). 1: divider output forced to high. 4 divider 0 start high selects clock output to start high or start low. 0: start low (default). 1: start high. [3:0] divider 0 phase offset phase offset (default = 0x0). 0x192 1 divider 0 direct to output connect out0 and out1 to divider 0 or directly to vco or clk. 0: out0 and out1 are connected to divider 0 (default). 1: if register 0x1e1[1:0] = 10b, the vco is routed directly to out0 and out1. if register 0x1e1[1:0] = 00b, the clk is routed directly to out0 and out1. if register 0x1e1[1:0] = 01b, there is no effect. 0 divider 0 dccoff duty-cycle correction function. 0: enable duty-cycle correction (default). 1: disable duty-cycle correction. 0x196 [7:4] divider 1 low cycles number of clock cycles of the divider inp ut during which divider output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] divider 1 high cycles number of clock cycles (minus 1) of the divider input during which divider output stays high. a value of 0x0 means that the divider is high for one input clock cycle (default = 0x0). 0x197 7 divider 1 bypass bypass and power-down th e divider; route input to divider output. 0: use divider (default). 1: bypass divider. 6 divider 1 nosync nosync. 0: obey chip-level sync signal (default). 1: ignore chip-level sync signal. 5 divider 1 force high force divider output to high. this requires that nosync (bit 6) also be set. 0: divider output forced to low (default). 1: divider output forced to high.
ad9517-1 rev. a | page 72 of 80 reg. addr. (hex) bits name description 0x197 4 divider 1 start high selects clock output to start high or start low. 0: start low (default). 1: start high. [3:0] divider 1 phase offset phase offset (default = 0x0). 0x198 1 divider 1 direct to output connect out2 and out3 to divider 2 or directly to vco or clk. 0: out2 and out3 are connected to divider 1 (default). 1: if register 0x1e1[1:0] = 10b, the vco is routed directly to out2 and out3. if register 0x1e1[1:0] = 00b, the clk is routed directly to out2 and out3. if register 0x1e1[1:0] = 01b, there is no effect. 0 divider 1 dccoff duty-cycle correction function. 0: enable duty-cycle correction (default). 1: disable duty-cycle correction. table 59. lvds/cmos channel dividers reg. addr. (hex) bits name description 0x199 [7:4] low cycles divider 2.1 number of clock cycles (minus 1) of 2.1 di vider input during which 2.1 output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] high cycles divider 2.1 number of clock cycles (minus 1) of 2.1 divi der input during which 2.1 output stays high. a value of 0x0 means that the divider is hi gh for one input clock cycle (default = 0x0). 0x19a [7:4] phase offset divider 2.2 refer to lvds/cmos channel divider function description (default = 0x0). [3:0] phase offset divider 2.1 refer to lvds/cmos channel divider function description (default = 0x0). 0x19b [7:4] low cycles divider 2.2 number of clock cycles (minus 1) of 2.2 di vider input during which 2.2 output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] high cycles divider 2.2 number of clock cycles (minus 1)of 2.2 divider input during which 2.2 output stays high. a value of 0x0 means that the divider is high for one input clock cycle (default = 0x0). 0x19c 5 bypass divider 2.2 bypass (and power-down) 2.2 divider logic, route clock to 2.2 output. 0: do not bypass (default). 1: bypass. 4 bypass divider 2.1 bypass (and power-down) 2. 1 divider logic, route clock to 2.1 output. 0: do not bypass (default). 1: bypass. 3 divider 2 nosync nosync. 0: obey chip-level sync signal (default). 1: ignore chip-level sync signal. 2 divider 2 force high force divider 2 output high. requires that nosync also be set. 0: force low (default). 1: force high. 1 start high divider 2.2 divider 2.2 start high/low. 0: start low (default). 1: start high. 0 start high divider 2.1 divider 2.1 start high/low. 0: start low (default). 1: start high. 0x19d 0 divider 2 dccoff duty-cycle correction function. 0: enable duty-cycle correction (default). 1: disable duty-cycle correction. 0x19e [7:4] low cycles divider 3.1 number of clock cycles (minus 1) of 3.1 di vider input during which 3.1 output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] high cycles divider 3.1 number of clock cycles (minus 1) of 3.1 divi der input during which 3.1 output stays high. a value of 0x0 means that the divider is hi gh for one input clock cycle (default = 0x0).
ad9517-1 rev. a | page 73 of 80 reg. addr. (hex) bits name description 0x19f [7:4] phase offset divider 3.2 refer to lvds/cmos channel divider function description (default = 0x0). [3:0] phase offset divider 3.1 refer to lvds/cmos channel divider function description (default = 0x0). 0x1a0 [7:4] low cycles divider 3.2 number of clock cycles (minus 1) of 3.2 di vider input during which 3.2 output stays low. a value of 0x0 means that the divider is lo w for one input clock cycle (default = 0x0). [3:0] high cycles divider 3.2 number of clock cycles (minus 1) of 3.2 di vider input during which 3.2 output stays high. a value of 0x0 means that the divider is hi gh for one input clock cycle (default = 0x0). 0x1a1 5 bypass divider 3.2 bypass (and power-down) 3.2 divider logic; route clock to 3.2 output. 0: do not bypass (default). 1: bypass. 4 bypass divider 3.1 bypass (and power-down) 3. 1 divider logic; route clock to 3.1 output. 0: do not bypass (default). 1: bypass. 3 divider 3 nosync nosync. 0: obey chip-level sync signal (default). 1: ignore chip-level sync signal. 2 divider 3 force high force divider 3 output high. requires that nosync also be set. 0: force low (default). 1: force high. 1 start high divider 3.2 divider 3.2 start high/low. 0: start low (default). 1: start high. 0 start high divider 3.1 divider 3.1 start high/low. 0: start low (default). 1: start high. 0x1a2 0 divider 3 dccoff duty-cycle correction function. 0: enable duty-cycle correction (default). 1: disable duty-cycle correction.
ad9517-1 rev. a | page 74 of 80 table 60. vco divider and clk input reg. addr (hex) bits name description 0x1e0 [2:0] vco divider 2 1 0 divide 0 0 0 2. 0 0 1 3. 0 1 0 4 (default). 0 1 1 5. 1 0 0 6. 1 0 1 output static. note that setting the vco divider static should occur only after vco calibration. 1 1 0 output static. note that setting the vco divider static should occur only after vco calibration. 1 1 1 output static. note that setting the vco divider static should occur only after vco calibration. 0x1e1 4 power down clock input section power down the clock input section (including clk buffer, vco divider, and clk tree). 0: normal operation (default). 1: power-down. 3 power down vco clock interface power down the interface block between vco and clock distribution. 0: normal operation (default). 1: power-down. 2 power down vco and clk power down both vco and clk input. 0; normal operation (default). 1: power-down. 0x1e1 1 select vco or clk select either the vco or the clk as the input to vco divider. 0: select external clk as input to vco divider (default). 1: select vco as input to vco divider; cannot bypass vco divider when this is selected. 0 bypass vco divider bypass or use the vco divider. 0: use vco divider (default). 1: bypass vco divider; cannot select vco as input when this is selected. table 61. system reg. addr. (hex) bits name description 0x230 2 power down sync power down the sync function. 0: normal operation of the sync function (default). 1: power down sync circuitry. 1 power down distribution reference power down the reference for distribution section. 0: normal operation of the referenc e for the distribution section (default). 1: power down the reference for the distribution section. 0 soft sync the soft sync bit works the same as the sync pin, except that the polarity of the bit is reversed. that is, a high level forces selected channels into a predetermined static state, and a 1-to-0 transition triggers a sync. 0: same as sync high (default). 1: same as sync low. table 62. update all registers reg. addr (hex) bits name description 0x232 0 update all registers this bit must be set to 1 to transfer the contents of the buffer registers into the active registers, which happens on the next sclk rising edge. this bit is self-clearing; that is, it does not have to be set back to 0. 1 (self-clearing): update all active regist ers to the contents of the buffer registers.
ad9517-1 rev. a | page 75 of 80 applications information on the sampling clock. considering an ideal adc of infinite resolution where the step size and quantization error can be ignored, the available snr can be expressed approximately by frequency planning using the ad9517 the ad9517 is a highly flexible pll. when choosing the pll settings and version of the ad9517, keep in mind the following guidelines. ? ? ? ? ? ? ? ? = j a tf snr 2 1 log20(db) the ad9517 has the following four frequency dividers: the reference (or r) divider, the feedback (or n) divider, the vco divider, and the channel divider. when trying to achieve a particularly difficult frequency divide ratio requiring a large amount of frequency division, some of the frequency division can be done by either the vco divider or the channel divider, thus allowing a higher phase detector frequency and more flexibility in choosing the loop bandwidth. where: f a is the highest analog frequency being digitized. t j is the rms jitter on the sampling clock. figure 69 shows the required sampling clock jitter as a function of the analog frequency and effective number of bits (enob). f a (mhz) snr (db) enob 10 1k 100 30 40 50 60 70 80 90 100 110 6 8 10 12 14 16 18 t j = 1 0 0 f s 2 0 0 f s 4 0 0 f s 1 p s 2 p s 1 0 p s snr = 20log 1 2 f a t j 06425-044 within the ad9517 family, lower vco frequencies generally result in slightly lower jitter. the difference in integrated jitter (from 12 khz to 20 mhz offset) for the same output frequency is usually less than 150 fs over the entire vco frequency range (1.45 ghz to 2.95 ghz) of the ad9517 family. if the desired frequency plan can be achieved with a version of the ad9517 that has a lower vco frequency, choosing the lower frequency part results in the lowest phase noise and the lowest jitter. however, choosing a higher vco frequency can result in more flexibility in frequency planning. choosing a nominal charge pump current in the middle of the allowable range as a starting point allows the designer to increase or decrease the charge pump current, and thus allows the designer to fine-tune the pll loop bandwidth in either direction. figure 69. snr and enob vs. analog input frequency see the an-756 application note and the an-501 application note at www.analog.com for more information. adisimclk is a powerful pll modeling tool that can be downloaded from www.analog.com . it is a very accurate tool for determining the optimal loop filter for a given application. many high performance adcs feature differential clock inputs to simplify the task of providing the required low jitter clock on a noisy pcb. (distributing a single-ended clock on a noisy pcb can result in coupled noise on the sample clock. differential distribution has inherent common-mode rejection that can provide superior clock performance in a noisy environment.) the ad9517 features both lvpecl and lvds outputs that provide differ- ential clock outputs, which enable clock solutions that maximize converter snr performance. the input requirements of the adc (differential or single-ended, logic level, termination) should be considered when selecting the best clocking/converter solution. using the ad9517 outputs for adc clock applications any high speed adc is extremely sensitive to the quality of its sampling clock. an adc can be thought of as a sampling mixer, and any noise, distortion, or timing jitter on the clock is combined with the desired signal at the analog-to-digital output. clock integrity requirements scale with the analog input frequency and resolution, with higher analog input frequency applications at 14-bit resolution being the most stringent. the theoretical snr of an adc is limited by the adc resolution and the jitter
ad9517-1 rev. a | page 76 of 80 lvpecl clock distribution the lvpecl outputs of the ad9517 provide the lowest jitter clock signals that are available from the ad9517. the lvpecl outputs (because they are open emitter) require a dc termination to bias the output transistors. the simplified equivalent circuit in figure 58 shows the lvpecl output stage. in most applications, a lvpecl far-end thevenin termination (see figure 70 ) or y-termination (see figure 71 ) is recommended. in each case, the v s of the receiving buffer should match the vs_lvpecl. if it does not, ac coupling is recommended (see figure 72 ). v s_lvpecl lvpecl 50 ? 50 ? single-ended (not coupled) v s v s_drv lvpecl 127? 127 ? 83? 83? 06425-145 figure 70. dc-coupled 3.3 v lvpe cl far-end thevenin termination v s_lvpecl lvpecl z 0 = 50 ? v s = 3.3 v lvpecl 50? 50? 50? z 0 = 50 ? 06425-147 figure 71. dc-coupled 3.3 v lvpecl y-termination v s_lvpecl lvpecl 100? differential (coupled) transmission line v s lvpecl 100? 0.1nf 0.1nf 200? 200 ? 06425-146 figure 72. ac-coupled lvpecl with parallel transmission line lvpecl y-termination is an elegant termination scheme that uses the fewest components and offers both odd- and even-mode impedance matching. even-mode impedance matching is an important consideration for closely coupled transmission lines at high frequencies. its main drawback is that it offers limited flexibility for varying the drive strength of the emitter-follower lvpecl driver. this can be an important consideration when driving long trace lengths but is usually not an issue. in the case shown in figure 71 , where vs_lvpecl = 2.5 v, the 50 termination resistor that is connected to ground should be changed to 19 . thevenin-equivalent termination uses a resistor network to provide 50 termination to a dc voltage that is below v ol of the lvpecl driver. in this case, vs_lvpecl on the ad9517 should equal v s of the receiving buffer. although the resistor combination shown in figure 71 results in a dc bias point of vs_lvpecl ? 2 v, the actual common-mode voltage is vs_lvpecl ? 1.3 v because additional current flows from the ad9517 lvpecl driver through the pull-down resistor. the circuit is identical when vs_lvpecl = 2.5 v, except that the pull-down resistor is 62.5 and the pull-up is 250 . lvds clock distribution the ad9517 provides four clock outputs (out4 to out7) that are selectable as either cmos or lvds level outputs. lvds is a differential output option that uses a current mode output stage. the nominal current is 3.5 ma, which yields 350 mv output swing across a 100 resistor. an output current of 7 ma is also available in cases where a larger output swing is required. the lvds output meets or exceeds all ansi/tia/eia-644 specifications. a recommended termination circuit for the lvds outputs is shown in figure 73 . v s lvds 100? differential (coupled) v s lvds 100 ? 06425-047 figure 73. lvds output termination see the an-586 application note at www.analog.com for more information on lvds.
ad9517-1 rev. a | page 77 of 80 termination at the far end of the pcb trace is a second option. the cmos outputs of the ad9517 do not supply enough current to provide a full voltage swing with a low impedance resistive, far-end termination, as shown in figure 75 . the far-end termination network should match the pcb trace impedance and provide the desired switching point. the reduced signal swing may still meet receiver input requirements in some applications. this can be useful when driving long trace lengths on less critical nets. cmos clock distribution the ad9517 provides four clock outputs (out4 to out7) that are selectable as either cmos or lvds level outputs. when selected as cmos, each output becomes a pair of cmos outputs, each of which can be individually turned on or off and set as noninverting or inverting. these outputs are 3.3 v cmos compatible. whenever single-ended cmos clocking is used, some of the following general guidelines should be used. cmos cmos 10? 50? 100? 100? v s 0 6425-077 point-to-point nets should be designed such that a driver has only one receiver on the net, if possible. this allows for simple termination schemes and minimizes ringing due to possible mismatched impedances on the net. figure 75. cmos output wi th far-end termination series termination at the source is generally required to provide transmission line matching and/or to reduce current transients at the driver. the value of the resistor is dependent on the board design and timing requirements (typically 10 to 100 is used). because of the limitations of single-ended cmos clocking, consider using differential outputs when driving high speed signals over long traces. the ad9517 offers both lvpecl and lvds outputs that are better suited for driving long traces where the inherent noise immunity of differential signaling provides superior performance for clocking converters. cmos outputs are also limited in terms of the capacitive load or trace length that they can drive. typically, trace lengths of less than 3 inches are recommended to preserve signal rise/fall times and preserve signal integrity. cmos cmos 10? 60.4 ? (1.0 inch) microstrip 06425-076 figure 74. series termination of cmos output
ad9517-1 rev. a | page 78 of 80 outline dimensions * compliant to jedec standards mo-220-vkkd-2 with exception to exposed pad dimension. 090209-a for proper connection of the exposed pad, refer to the pin configuration and function descriptions section of this data sheet. 6.75 bsc sq 7.00 bsc sq 1 48 12 13 37 36 24 25 * 5.65 5.50 sq 5.35 0.50 0.40 0.30 0.30 0.23 0.18 0.80 max 0.65 typ 5.50 ref coplanarity 0.08 exposed pad (bottom view) 0.20 ref 1.00 0.85 0.80 0.05 max 0.02 nom seating plane 12 max top view 0.60 max 0.60 max pin 1 indicator 0.50 bsc pin 1 indicator 0.25 min figure 76. 48-lead lead frame chip scale package [lfcsp_vq] 7 mm 7 mm body, very thin quad cp-48-8 dimensions shown in millimeters pin 1 indicator top view 6.75 bsc sq 7.00 bsc sq 1 48 12 13 37 36 24 25 5.25 5.10 sq 4.95 0.50 0.40 0.30 0.30 0.23 0.18 0.50 bsc 12 max 0.20 ref 0.80 max 0.65 typ 1.00 0.85 0.80 5.50 ref 0.05 max 0.02 nom 0.60 max 0.60 max pin 1 indicator coplanarity 0.08 seating plane 0.25 min exposed pad (bottom view) compliant to jedec standards mo-220-vkkd-2 080108-a for proper connection of the exposed pad, refer to the pin configuration and function descriptions section of this data sheet. figure 77. 48-lead lead frame chip scale package [lfcsp_vq] 7 mm 7 mm body, very thin quad cp-48-1 dimensions shown in millimeters ordering guide model 1 temperature range package description package option ad9517-1abcpz 2 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-8 ad9517-1abcpz-rl7 2 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-8 AD9517-1BCPZ ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 AD9517-1BCPZ-reel7 ?40c to +85c 48-lead lead frame chip scale package (lfcsp_vq) cp-48-1 ad9517-1a/pcbz 2 evaluation board ad9517-1/pcbz evaluation board 1 z = rohs compliant part. 2 recommended for use in new de signs; reference pcn 09_156.
ad9517-1 rev. a | page 79 of 80 notes
ad9517-1 rev. a | page 80 of 80 notes ?2007C2010 analog devices, inc. all rights reserved. trademarks and registered trademarks are the prop erty of their respective owners. d06425-0-1/10(a)

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